Vehicle accessory microphone

ABSTRACT

A microphone assembly includes one or more transducers ( 2210 ) that are positioned in one or more housings. A preprocessing circuit ( 2215 ) includes a inverted comb filter ( 2245 ) for eliminating predetermined frequencies between harmonics of the human voice in a predetermined frequency range. A processing circuit ( 2220 ) coupled to the preprocessing circuit ( 2215 ) is used for outputting an electrical signal such that the transducers ( 2210 ) used in combination with the processing circuit ( 2220 ) very effectively cancels noise. The microphone assembly can be employed in a vehicle accessory such as a vehicular mirror.

This application claims priority to U.S. Pat. No. 6,882,734; U.S. Pat. No. 7,120,261; U.S. Pat. No. 6,614,911; and U.S. application Ser. No. 10/492,490.

BACKGROUND OF THE INVENTION

The present invention pertains to microphones, and more particularly to a microphone associated with a vehicle accessory such as a rearview mirror assembly or the housing of a rear vision display device.

It has long been desired to provide improved microphone performance in devices such as communication devices and voice recognition devices that operate under a variety of different ambient noise conditions. Communication devices supporting hands-free operation permit the user to communicate through a microphone of a device that is not held by the user. Because of the distance between the user and the microphone, these microphones often detect undesirable noise in addition to the user's speech. The noise is difficult to attenuate. Hands-free communication systems for vehicles are particularly challenging due to the dynamically varying ambient noise that is present. For example, bi-directional communication systems such as two-way radios, cellular telephones, satellite telephones, and the like, are used in vehicles, such as automobiles, trains, airplanes and boats. For a variety of reasons, it is preferable for the communication devices of these systems to operate hands-free, such that the user need not hold the device while talking, even in the presence of high ambient noise levels subject to wide dynamic fluctuations.

Bi-directional communication systems include an audio speaker and a microphone. In order to improve hands-free performance in a vehicle communication system, a microphone is typically mounted near the driver's head. For example, a microphone is commonly attached to the vehicle visor or headliner using a fastener such as a clip, adhesive, hook and loop fastening tape (such as VELCRO brand fastener), or the like. The audio speaker associated with the communication system is preferably positioned remote from the microphone to assist in minimizing feedback from the audio speaker to the microphone. It is common, for example, for the audio speaker to be located in a vehicle adaptor, such as a hang-up cup or a cigarette lighter plug used to provide energizing power from the vehicle electrical system to the communication device. Thus, although the communication system designer knows the position of the audio speaker in advance, the position of the microphone is unknown as the user can position the microphone where they choose. The position of the microphone relative to the person speaking will determine the level of the speech signal output by the microphone and may affect the signal-to-noise ratio. The position of the microphone relative to the audio speaker will impact on feedback between the speaker and microphone. Accordingly, the performance of the audio system is subject to the user's installation of the microphone. Additionally, the microphone will typically include a wire, which if it is mounted to the surface of the vehicle interior, will not be aesthetically pleasing. Alternatively, if the wire is to be mounted behind the interior lining, the vehicle interior must be disassembled and then reattached so that the wire can be hidden, which may result in parts that rattle loudly or hang loosely from the vehicle frame.

One potential solution to avoid these difficulties is disclosed in U.S. Pat. No. 4,930,742, entitled “REARVIEW MIRROR AND ACCESSORY MOUNT FOR VEHICLES”, issued to Schofield et al. on Jun. 5, 1990, which uses a microphone in a mirror mounting support. Although locating the microphone in the mirror support provides the system designer with a microphone location that is known in advance, and avoids the problems associated with mounting the microphone after the vehicle is manufactured, there are a number of disadvantages to such an arrangement. Because the mirror is positioned between the microphone and the person speaking into the microphone, a direct unobstructed path from the user to the microphone is precluded. Additionally, the location of the microphone on the windshield detrimentally impacts on microphone design flexibility and overall noise performance of the microphone.

U.S. Pat. Nos. 5,940,503, 6,026,162, 5,566,224, 5,878,353, and D 402,905 disclose rearview mirror assemblies with a microphone mounted in the bezel of the mirror. None of these patents, however, disclose the use of acoustic ports facing multiple directions nor do they disclose microphone assemblies utilizing more than one microphone transducer. The disclosed microphone assemblies do not incorporate sufficient noise suppression components to provide output signals with relatively high signal-to-noise ratios, and do not provide a microphone having a directional sensitivity pattern or a main lobe directed forward of the housing and attenuating signals originating from the sides of the housing.

It is highly desirable to provide voice recognition systems in association with vehicle communication systems, and most preferably, such a system would enable hands-free operation. Hands-free operation of a device used in a voice recognition system is a particularly challenging application for microphones, as the accuracy of a voice recognition system is dependent upon the quality of the electrical signal representing the user's speech. Conventional hands-free microphones are not able to provide the consistency and predictability of microphone performance needed for such an application in a controlled environment such as an office, let alone in an uncontrolled and noisy environment such as an automobile.

Commonly-assigned U.S. Pat. No. 6,882,734 and PCT Application Publication No. WO 01/37519 A2 also disclose various embodiments of rearview mirror-mounted microphone assemblies. In those embodiments, at least one microphone transducer is typically aimed at the driver of the vehicle. This usually results in the microphone assembly being visibly mounted to the top or bottom surface of the mirror housing. Such visibility raises certain styling concerns as well as performance issues when used in certain environments and in combination with digital signal processing circuits.

It has long been desired to provide improved microphone performance in devices such as communication devices and voice recognition devices that operate under a variety of different ambient noise conditions. Communication devices supporting hands-free operation permit the user to communicate through a microphone of a device that is not held by the user. Because of the distance between the user and the microphone, these microphones often detect undesirable noise in addition to the user's speech. The noise is difficult to attenuate. Hands-free communication systems for vehicles are particularly challenging due to the dynamically varying ambient noise that is present. For example, bi-directional communication systems such as two-way radios, cellular telephones, satellite telephones, and the like, are used in vehicles, such as automobiles, trains, airplanes and boats. For a variety of reasons, it is preferable for the communication devices of these systems to operate hands-free, such that the user need not hold the device while talking, even in the presence of high ambient noise levels subject to wide dynamic fluctuations. Accordingly, there is a need for a microphone for a vehicle providing improved hands-free performance and preferably enabling voice recognition operation when a digital signal processing circuit is utilized.

BRIEF DESCRIPTION OF THE DRAWINGS

The subject matter that is regarded as the invention is particularly pointed out and distinctly claimed in the claim portion that concludes the specification. The invention, together with further objects and advantages thereof, may best be understood by reference to the following description taken in conjunction with the accompanying drawings, where like numerals represent like components, and in which:

FIG. 1 is a top plan view illustrating a vehicle with a portion of the roof cut away;

FIG. 2 is a front, bottom and left side perspective view illustrating a rearview mirror assembly and fragmentary mirror support used in the vehicle of FIG. 1;

FIG. 3 is a top exploded view illustrating a microphone assembly used in the mirror according to FIG. 2;

FIG. 4 is a bottom plan view illustrating the microphone assembly according to FIG. 2;

FIG. 5 is a bottom plan view illustrating a transducer mount in the microphone assembly according to FIG. 3;

FIG. 6 is cross-sectional view taken along plane 6-6 in FIG. 4 illustrating the microphone assembly according to FIG. 3;

FIG. 7 is a top plan view illustrating the microphone assembly according to FIG. 5 with the circuit board removed to view show the transducers in transducer mount;

FIG. 8 is a circuit schematic partially in block diagram form illustrating a circuit employed with the microphone assembly of FIGS. 3-7;

FIG. 9 is a top plan view schematic representation illustrating the sound channel for the transducers of the microphone assembly according to FIGS. 1-7;

FIG. 10 is a top plan view schematic representation illustrating the sound channel for an alternate transducer arrangement for the microphone assembly;

FIG. 11 is a top plan view schematic representation illustrating the sound channel for another alternate transducer arrangement for the microphone assembly;

FIG. 12 is a circuit schematic partially in block diagram form illustrating a circuit for use with the microphone according to claim 11;

FIG. 13 is a circuit schematic partially in block diagram form illustrating an auto-calibration circuit for use with the microphone assembly;

FIG. 14 is a flow chart representing operation of the controller of FIG. 12;

FIG. 15 is a cross-sectional view of the microphone according to FIG. 10 taken along the longitudinal axis of the microphone;

FIG. 16 is a perspective view of a microphone assembly constructed in accordance with another embodiment of the present invention;

FIG. 17 is an exploded perspective view of a microphone assembly shown in FIG. 16;

FIG. 18 is a front isometric view of an embodiment of a rearview mirror assembly constructed in accordance with another embodiment of the present invention;

FIG. 19 is a rear isometric view of an embodiment of a rearview mirror assembly shown in FIG. 18;

FIG. 20 is a side elevation of the rearview mirror assembly shown in FIGS. 18 and 19;

FIG. 21 is an exploded perspective view of a microphone assembly constructed in accordance with another embodiment of the present invention;

FIGS. 22A-22D are plots of polar patterns at different frequencies as obtained from a microphone assembly constructed in accordance with the present invention with a cover over the transducers;

FIGS. 23A-23D are plots of polar patterns at different frequencies as obtained from a microphone assembly constructed in accordance with the present invention without a cover over the transducers;

FIG. 24 is a side elevational view of a portion of a rearview mirror assembly having a deflector, a fine turbulence generator and a microphone assembly according to another embodiment of the present invention;

FIG. 25 is a top view of the portion of the rearview mirror assembly having the deflector, the fine turbulence generator and the microphone assembly that are shown in FIG. 24;

FIG. 26 is a rear view of the portion of the rearview mirror assembly having the deflector, the fine turbulence generator and the microphone assembly that are shown in FIGS. 24 and 25;

FIG. 27 is an electrical circuit diagram in block form showing an embodiment of a microphone processing circuit of the present invention;

FIG. 28A is an electrical circuit diagram in schematic form showing an exemplary high pass filter that may be used in the circuit shown in FIG. 27;

FIG. 28B is an electrical circuit diagram in schematic form showing an exemplary all-pass phase shifter that may be used in the circuit shown in FIG. 27;

FIG. 28C is an electrical circuit-diagram in schematic form showing an exemplary summing circuit that may be used in the circuit shown in FIG. 27;

FIG. 28D is an electrical circuit diagram in schematic form showing an exemplary three-pole high pass filter that may be used in the circuit shown in FIG. 27;

FIG. 28E is an electrical circuit diagram in schematic form showing an exemplary buffer circuit that may be used in the circuit shown in FIG. 27;

FIG. 29A is a plot of three frequency response curves of a second order microphone assembly with sound originating from three different directions;

FIG. 29B is a plot of a frequency response curve of the second order microphone processing circuit shown in FIG. 27 but without the all-pass phase shifter;

FIG. 29C is a plot of four frequency response curves of the second order microphone processing circuit shown in FIG. 27 with sound originating from four different directions;

FIG. 30 is block diagram illustrating a microphone system constructed in accordance with the present invention;

FIG. 31 is a process diagram for the digital signal processor shown in FIG. 30 according to a first embodiment;

FIG. 32 is an exemplary plot of a FFT of an audio signal received from a typical transducer while receiving both noise and a user's speech;

FIG. 33 is a graph of an ideal inverted comb filter for filtering the audio signal whose FFT is illustrated in FIG. 32;

FIG. 34 is a process diagram for the digital signal processor shown in FIG. 30 according to a second embodiment;

FIG. 35 is a simplified electrical schematic of a prior art microphone assembly coupled to an electronic assembly;

FIG. 36 is a simplified electrical schematic of a microphone assembly coupled to an electronic assembly through a microphone interface, according to an embodiment of the present invention;

FIG. 37 is a simplified electrical schematic of a microphone assembly coupled to an electronic assembly through a microphone interface, according to another embodiment of the present invention;

FIG. 38 is a simplified electrical schematic of a microphone assembly coupled to an electronic assembly through a microphone interface, according to yet another embodiment of the present invention;

FIG. 39A is an elevational view of the front of a rearview mirror assembly constructed in accordance with an alternative embodiment of the present invention;

FIG. 39B is an elevational view of the rear of the rearview mirror assembly shown in FIG. 39A;

FIG. 39C is an elevational view of the side of the rearview mirror assembly shown in FIGS. 39A and 39B;

FIG. 39D is a plan view of the top of the rearview mirror assembly shown in FIGS. 39A-39C;

FIG. 40 is a graph showing four plots representing the output of various microphone assemblies when the vehicle defroster is running at full speed;

FIGS. 41A-41D are perspective views showing a rearview mirror incorporating a microphone assembly in accordance with another embodiment of the present invention;

FIG. 42 is a plan view of the top of another embodiment of the microphone assembly of the present invention, shown with the housing in outline form;

FIGS. 43A and 43B are perspective views of a housing that may be used for a microphone assembly constructed in accordance with the embodiment of the present invention shown in FIG. 42;

FIG. 44 are plots of polar patterns for both of the two transducers as obtained from a microphone assembly constructed in accordance with the embodiment of the present invention shown in FIGS. 42, 43A and 43B;

FIGS. 45A and 45B are perspective views of an alternative housing that may be used for a microphone assembly constructed in accordance with the embodiment of the present invention shown in FIG. 42;

FIG. 46 are plots of polar patterns for both of the two transducers as obtained from a microphone assembly constructed in accordance with the embodiment of the present invention shown in FIGS. 42, 45A and 45B;

FIG. 47 is a plan view of the top of another embodiment of the microphone assembly of the present invention, shown with the housing in outline form;

FIGS. 48A and 48B are perspective views of a housing that may be used for a microphone assembly constructed in accordance with the embodiments of the present invention shown in FIGS. 47 and 49;

FIG. 49 is a plan view of the top of another embodiment of the microphone assembly of the present invention, shown with the housing in outline form;

FIGS. 50A-50E show a rearview mirror assembly incorporating a microphone assembly in accordance with another embodiment of the present invention;

FIG. 51 is an electrical circuit diagram in block form showing a noise cancellation circuit that may be used with the present invention; and

FIG. 52 is an electrical circuit diagram in block form showing an alternative noise cancellation circuit that may be used with the present invention.

FIG. 53A is an elevational view of the front of a rearview mirror assembly incorporating a microphone assembly in accordance with a first embodiment of the present invention;

FIG. 53B is an elevational view of the rear of the rearview mirror assembly incorporating a microphone assembly in accordance with the first embodiment of the present invention;

FIG. 53C is an elevational view of one side of the rearview mirror assembly incorporating a microphone assembly in accordance with the first embodiment of the present invention;

FIG. 53D is a plan view of the top of the rearview mirror assembly incorporating a microphone assembly in accordance with the first embodiment of the present invention;

FIG. 53E is an elevational view of one side of the rearview mirror assembly in partial cross-section taken along line E-E in FIG. 53B;

FIG. 54A is an elevational view of the rear of the rearview mirror assembly incorporating a microphone assembly in accordance with the second embodiment of the present invention;

FIG. 54B is an elevational view of one side of the rearview mirror assembly incorporating a microphone assembly in accordance with the second embodiment of the present invention;

FIG. 54C is a plan view of the top of the rearview mirror assembly incorporating a microphone assembly in accordance with the second embodiment of the present invention;

FIG. 54D is an elevational view of one side of the rearview mirror assembly in partial cross-section taken along line D-D in FIG. 54C;

FIG. 55 is an elevational view of the front of the microphone assembly of the second embodiment of the present invention;

FIG. 56 is a plan view of the top of the microphone assembly of the second embodiment of the present invention;

FIG. 57 is an elevational view of one end of the microphone assembly of the second embodiment of the present invention;

FIG. 58 is a cross-sectional view of the microphone assembly shown in FIG. 55 taken along line VII-VII;

FIG. 59 is a cross-sectional view of the microphone assembly shown in FIG. 55 taken along line VIII-VIII;

FIG. 60 is a cross-sectional view of the microphone assembly shown in FIG. 55 taken along line IX-IX;

FIG. 61 is a schematic top view of the microphone assembly of the second embodiment of the present invention;

FIG. 62 is an exploded perspective view of a portion of the microphone assembly of the second embodiment of the present invention;

FIG. 63 is a polar plot taken of a rearview mirror assembly of the present invention having a microphone assembly with a low acoustic resistance windscreen;

FIG. 64 is a comparative noise plot taken of two different rearview mirror assemblies of the present invention, one having a microphone assembly with a low acoustic resistance windscreen and the other one having a microphone assembly with a very high acoustic resistance windscreen;

FIG. 65 is a polar plot taken of a rearview mirror assembly of the present invention having a microphone assembly with a very high acoustic resistance windscreen, but with no acoustic dam;

FIG. 66 is a polar plot taken of a rearview mirror assembly of the present invention having a microphone assembly with a very high acoustic resistance windscreen and an acoustic dam;

FIG. 67 is a polar plot taken of a rearview mirror assembly of the present invention in a first orientation at 250 Hz and having a microphone assembly with a very high acoustic resistance windscreen and an acoustic dam;

FIG. 68 shows various polar plots taken of a rearview mirror assembly of the present invention in a first orientation at various frequencies between 300 Hz and 2 kHz and having a microphone assembly with a very high acoustic resistance windscreen and an acoustic dam;

FIG. 69 shows various polar plots taken of a rearview mirror assembly of the present invention in a first orientation at various frequencies between 3 Hz and 6 kHz and having a microphone assembly with a very high acoustic resistance windscreen and an acoustic dam;

FIG. 70 shows various polar plots taken of a rearview mirror assembly of the present invention in a second orientation at various frequencies between 300 Hz and 1 kHz and having a microphone assembly with a very high acoustic resistance windscreen and an acoustic dam;

FIG. 71 shows various polar plots taken of a rearview mirror assembly of the present invention in a second orientation at various frequencies between 3 kHz and 6 kHz and having a microphone assembly with a very high acoustic resistance windscreen and an acoustic dam;

FIG. 72 shows various polar plots taken of a rearview mirror assembly of the present invention in a second orientation at various frequencies between 6.5 Hz and 8 kHz and having a microphone assembly with a very high acoustic resistance windscreen and an acoustic dam; and

FIG. 73 is a schematic view of a microphone assembly of the present invention; and

FIG. 74 is a perspective view of the microphone assembly shown in FIG. 73.

DETAILED DESCRIPTION OF THE INVENTION

The microphone assemblies of the present invention are associated with an interior rearview mirror and have superior performance even in the presence of noise. The microphone assemblies enhance the performance of hands-free devices with which they are associated, including highly sensitive applications such as voice recognition for a telecommunication system, by improving the signal-to-noise ratio of the microphone assembly output. The microphone assemblies eliminate mechanically induced noise and provide the designer with significant freedom with respect to selection of the microphone assembly's sensitivity, frequency response and polar pattern. Additionally, circuitry can be provided for the transducer to generate an audio signal from the transducer output that has a high signal-to-noise ratio.

As seen in FIG. 1, a vehicle 100 includes an interior rearview mirror assembly 101 by which the vehicle operator 103 (illustrated in phantom) can view a portion of the road behind the vehicle 100 without having to turn around. The rearview mirror assembly 101 is mounted to the vehicle windshield 105, or the vehicle's headliner, via a mirror mounting support 104, in a conventional manner that facilitates electrical connection of the rearview mirror to the vehicle's electrical system and permits driver adjustment of the mirror-viewing angle.

The rearview mirror assembly 101 according to a first embodiment is enlarged in FIG. 2. The mirror assembly 101 includes an elongated housing 206 pivotably carried on mirror support 104. The mirror 202 may be any conventional interior rearview mirror, such as a prismatic mirror of the type used with a mirror housing manually adjustable for daytime and nighttime operation, or a multiple element mirror effecting automatic reflectivity adjustment, such as an electrooptic or electrochromic mirror. The elongated housing 206 may be of any conventional manufacture such as integrally molded plastic.

The rearview mirror assembly 101 further includes a microphone assembly 208 that is preferably mounted to the housing 206 at a location visible to the vehicle driver 103 or at a position which is direct line of sight between the speaker's mouth and the microphone. It is advantageous for the microphone assembly 208 to be positioned on the mirror housing 206 as the mirror assembly is movably carried on the support 104. The driver 103 (FIG. 1) will typically adjust the position of the mirror 202 and housing 206 to reflect images visible through the rear window 109 of the vehicle 100. When making such an adjustment for viewing angle, the driver 103 adjusts the mirror 202 toward their eyes by moving housing 206, which will simultaneously direct the front of microphone assembly 208 toward the driver. However, the microphone assembly could be mounted in other vehicle accessories, such as a visor, an overhead console, a vehicle trim component such as a headliner or an A-pillar cover, a center console, an on-windshield console, or the like.

A first embodiment of the microphone assembly 208 will now be described in greater detail with respect to FIGS. 3-7. The microphone assembly includes a microphone housing 300, a transducer mount 302, a first transducer 304, a second transducer 306, and a circuit board 308. The microphone housing 300 (FIGS. 3 and 4) is generally cylindrical, having a round foot print and a low profile, although the housing could have a generally square foot print, an elongated elliptical or rectangular foot print, or any other shape desired by the microphone designer. The microphone housing 300 includes front ports 312 that face the driver 103 and rear ports 314 that face away from the driver 103. The ports 312 and 314 provide a sound passage through the microphone housing. The ports 312, 314 can have any suitable opening shape or size. The housing also includes posts 316, 317 used to hold the microphone assembly 208 together, as described in greater detail herein below. A rail 318 on the inside surface of housing 300 is shaped to receive a portion of mount 302. When received in the rail, mount 302 is positioned with the transducer 304 and 306 sound channels properly aligned with the ports 312, 314. The housing also includes mounting tabs 320 for insertion into openings (not shown) in the lower surface of housing 206. For example, the tabs can be generally L-shaped in profile for insertion into the housing 300. After tabs 320 are inserted into housing 206, the microphone housing 300 is locked to the mirror housing 206 by rotating the microphone to a locked position, thereby securing the microphone assembly 208 on the housing assembly 101. Alternately, the tabs 320 can be elongate snap connectors that slide into an opening (not shown) in the bottom surface of the mirror housing and snap into engagement with the inside surface of the mirror housing 206 after fall insertion. The microphone housing 300 can be integrally molded plastic, stamped metal, or of any other suitable manufacture.

The transducer mount 302 is configured such that it is pressed into the housing 300 and is slightly compressed between circuit board 308 and housing 300. The transducer mount provides acoustic seals for the transducers 304 and 306, and with the circuit board 308 and housing 300, defines acoustic channels, or sound passages, to the front and rear faces of the transducers 304, 306, as described in greater detail below. The mount 302 includes webs 324 between walls 332 and webs 325 between walls 333 that extend outwardly from the core of mount 302 to provide sound passages, and also help to position mount 302 in the housing 300. Projections 326, 327 are located on opposite ends of mount 302 to help position mount 302 in housing 300. Openings 328, 329 are provided in the webbing 324, 325 of mount 302 for passage of posts 316, 317. Cylindrical wells 330, 331 are provided in the core of transducer mount 302 for receipt of transducers 304, 306, respectively. Each of the wells 330, 331 includes a terminating wall 501 (FIG. 5) against which the front faces 500 of the transducers 304, 306 sit. The terminating walls 501 each include a channel 506, 508 that extends radially outward from the center of the well, which is the location of the front transducer aperture. The mount 302 can be of any suitable manufacture, such as a molded elastomer. In particular the mount 302 is resilient and non-conductive, and provides acoustic isolation. For example, the transducer mount 302 can be manufactured of urethane commercially available from Mobay, Inc.

The transducers 304 and 306 are preferably substantially identical. The transducers include a front aperture 502 which passes sound to the front surface of a transducer diaphragm and openings 337 (FIG. 3) in the back face that port sound to the back surface of the transducer diaphragm. The transducers include electrical leads 336 on the back face thereof for electrical connection to the conductive layer of circuit board 208. The transducers 304 and 306 can be any suitable, conventional transducers, such as electret, piezoelectric, or condenser transducers. The transducers may be, for example, electret transducers such as those commercially available from Matsushita of America (doing business as Panasonic), and may advantageously be unidirectional transducers. If electret transducers are employed, the transducers can be suitably conditioned to better maintain transducer performance over the life of the microphone assembly 208. For example, the diaphragms of the transducers 304, 306 can be baked prior to assembly into the transducers.

The circuit board 308 has a conductive layer, on surface 334, etched and electrically connected to the transducer leads 336 of transducers 304, 306. The microphone leads 340 are connected to the transducer leads 336 by a circuit 800 (FIG. 8) mounted to the conductive layer of circuit board 308. Although circuit 800 can be mounted on the circuit board 308 in the microphone housing, it will be recognized that the circuit 800 can alternatively be mounted on a printed circuit board in the mirror housing 206, and further that in the case of an electrooptic mirror, such as an electrochromic mirror, the circuit 800 can be mounted on a common circuit board with the mirror electrical components, or the circuit 800 and the mirror electrical components can be mounted on separate circuit boards within the housing 206. The electrical connection of the microphone leads 340, the transducer leads 336, and the components of circuit 800, are preferably by electrical traces in the conductive layer of the circuit board, formed by conventional means such as etching, and vias extending through the dielectric substrate of the printed circuit board. The circuit board includes holes 350 and 352 for receipt of posts 316 and 317 on microphone housing 300. The posts 316, 317 are heat staked to the circuit board substrate after the posts are inserted through holes 350 and 352 to secure the connection of the circuit board to the housing 300 and insure that the microphone assembly provides acoustically isolated sound channels between the transducers 304, 306 and the ports 312, 314, as described in greater detail herein below.

To assemble the microphone assembly 208, the transducers 306 and 308 are mounted on the circuit board 308 by conventional means, such as by soldering transducer leads 336 to the conductive layer 334 of circuit board 308. It is envisioned that the transducer leads can alternatively be elongated posts that extend through vias in the printed circuit board, that the surface 360 can be a conductive layer, and that the components of circuit 800 can be located on surface 360 of the printed circuit board, connected between the transducer leads 336 and the microphone leads 340. Regardless of how the transducers 304 and 306 are mounted on the circuit board 308, the circuit board mounted transducers are pressed into the cylindrical wells 330, 331 in the mount 302. When fully inserted in the wells, the front faces 500 (FIG. 5) of the transducers 304, 306, are positioned against the terminating wall 501 of the wells 330, 331. The wall 501 of each of the wells 330, 331 includes a channel 506, 508 aligned with the openings 502 in the front face of the transducers 304, 306.

The partial assembly comprising mount 302, transducers 304, 306 and circuit board 308, is pressed into the housing 300. FIG. 7 illustrates the microphone assembly 208 with the printed circuit board 308 removed. The back surfaces of the transducers 304, 306, having multiple openings 337 and transducer leads 336, are visible from the open end of the cylindrical wells 330,331. When the transducers 304, 306 are fully inserted in the well, such that the front face 500 of the transducers are juxtaposed with the wall 501 terminating the well, a chamber is formed between the back surface of each of the transducers 304, 306 and the circuit board 308, as best shown in FIG. 6. A wall of the mount circumscribes the periphery of the transducer 306, 307, and a short channel 371, 373 extends from the well 330, 331 to the aperture 370, 372. The circumscribing wall provides an acoustic seal with the circuit board 308. Apertures 370, 372 connect the chamber, between each of the transducers 304, 306 and the circuit board 308, with the channels 510, 512, respectively. The chamber behind each of the transducers provides a sound passage from the back openings 337 of the transducers through channels 371, 373, 510, and 512 and ports 312, 314. When the mount 302 is fully inserted in the housing 300, the sound passages extending from the front face of each of the transducers to ports 312 and 314 are defined by the housing 300 and the mount 302. The sound passages extending from the back face of each of the transducers to ports 312 and 314 are defined by the housing 300, mount 302 and circuit board 308.

In particular the front opening 502 of transducer 306 is connected to the front ports 312 of the microphone housing 300 via the sound passage 506 as best shown in FIG. 6. The rear face openings 337 of the transducer 306 is acoustically coupled to the rear ports 314 via sound channel 373, aperture 372 and channel 510. Transducer 304 is coupled to the front ports 312 and the rear ports 314 in the same manner, but in the opposite phase. In particular, the front face of transducer 304 is acoustically coupled to the rear ports 314 via acoustic channel 508 (FIG. 5). The rear face openings 337 of the transducer 304 are acoustically coupled to the front ports 312 via channel 371, aperture 370, and channel 512. Signals originating from the front of the microphone assembly, which is the surface of the microphone assembly facing the driver, enter the front of transducer 306 and the back of transducer 304, whereas sound originating from the rear of the microphone assembly enter the front face of transducer 304 and the back face of transducer 306. Omni-directional sounds will be detected equally by the transducers, at opposite phases.

As illustrated in FIG. 6, the center axes C of the transducers 304, 306 are oriented at an angle of 90 degrees with respect to the longitudinal axes L_(B) and L_(F) of the channels 506, 508, 510, 512. Thus, the acoustic outputs from the two transducers lie on a common axis facing in opposite directions and perpendicular to the center axis C of the transducers.

The transducers 304 and 306 are electrically coupled to an operational amplifier 802 (FIG. 8) of circuit 800. In particular, transducer 306 is coupled to the inverting input of the operational amplifier 802 and transducer 304 is coupled to the non-inverting input of the operational amplifier. Resistor R8, connected between the transducer 306 and the inverting input of the operational amplifier 802, is preferably a potentiometer to permit manual balancing of the transducers. Alternatively, the resistor R12 connected between transducer 304 and the non-inverting input of the operational amplifier, or both resistors R10 and R12, can be implemented by potentiometers. It is also envisioned that a variable gain amplifier with an associated manually adjustable potentiometer can be inserted in one or both of the paths between transducers 304, 306 and operational amplifier 802. The operational amplifier may be implemented using any suitable operational amplifier, such as the TLC271 operational amplifier available from Texas Instruments, Inc. The manually adjustable potentiometer R8 is provided for varying the gain of the transducer path to permit adjustment of the signal level from transducer 306 such that both transducer 304, 306 paths produce the same signal gain (i.e., the signal gain through both transducers is equal). By providing identical gain through both transducers, omni-directional noise detected by both transducers will be completely cancelled at the output of the operational amplifier 802.

Acoustic signals generated by the vehicle driver, such as the driver's speech, will be input to the front of transducer 306 and the back of transducer 304, such that the speech will be present in the audio signal at the output of operational amplifier 302. Sound from the sides of the microphone assembly will be cancelled by the transducers 304, 306 and the operational amplifier 802. The most intense noise in a vehicle tends to originate from the sides and/or front of the vehicle. The microphone assembly 208 mounted on the rearview mirror 206, including amplifier 802, will significantly reduce noise as the bi-directional microphone assembly is not responsive to noise originating from the sides of the vehicle when mounted in the mirror assembly 101 which is generally aligned with the longitudinal axis of the vehicle. Furthermore, mechanical noise, such as that originating in the rearview mirror assembly 101, will be detected by both transducers 304, 306 equally, and thus will be cancelled out by the operational amplifier 802.

The output of the operational amplifier 802 is input to a 3-pole high pass filter and unity gain follower 804, having a cut-off at approximately 100-300 Hz, and preferably at 150 Hz. The filter removes noise below the voice frequency. Terminals 340 are coupled to the vehicle's electrical circuitry, which may for example include voice recognition circuitry, a cellular transceiver, a two-way radio, or any other control circuitry. The transistors Q1 and Q2 can be implemented using any suitable commercially available transistor elements, such as FFB2227 commercially available from Fairchild Semiconductor.

In summary, the bi-directional microphone assembly 208 is very responsive to voice signals from the driver 103 located in front of the mirror assembly 101, as signals from the front of the mirror will sum in operational amplifier 802. As a consequence, on-axis sound will experience a gain and the microphone assembly will have a high signal-to-noise ratio. It is envisioned that a gain of approximately 6 dB can be achieved by bi-directional microphone assembly 208. The microphone is highly directional, such that off-axis sound is attenuated, and even nulled, by the microphone. Further, the bi-directional microphone assembly 208 can employ any type of directional transducer, so long as identical transducers are employed.

The bi-directional microphone assembly 208 is schematically illustrated in FIG. 9, and alternate embodiments are schematically illustrated in FIGS. 10 and 11. As described above, the bi-directional microphone assembly 208 includes transducer 306, having its front face opening ported to the front ports 312 through channel 506 and its back face openings ported to the back ports 314 through channels 370, 371 and 510, and transducer 304, having its front face ported to the rear ports 314 through channel 508 and its rear face ported to the front port 312 through channels 372, 373 and 512. The bi-directional microphone assembly 208 thus has transducers mounted on the same lateral axis, but at opposite phases. An alternative to the bi-directional microphone assembly 208, is the hyper cardioid microphone assembly 1000 illustrated in FIG. 10. The hyper cardioid microphone assembly 1000 includes a front transducer 1002 having its front face acoustically coupled to port 1004 through channel 1005 and its back face acoustically coupled to port 1006 through channel 1009. The front face of a rear transducer 1008 is acoustically coupled to ports 1010 through channel 1011 and the rear face of transducer 1008 is acoustically coupled to port 1006 through channel 1012. The transducers are electrically coupled to an operational amplifier in the same manner that the transducers 304 and 306 are electrically coupled to operational amplifier 802. However, unlike bi-directional microphone assembly 208, for which identical transducers are selected, the transducers 1002 and 1008, and the variable gain balance circuit 802, are selected and operated such that the front transducer 1002 produces a greater sensitivity than the back transducer 1008 while maintaining a null of the vibration created signals.

The microphone assembly 1000 may be advantageous in applications wherein the noise incident on the microphone assembly is generally random and omni directional, or in an environment where the front lobe of the microphone needs to be larger to accommodate off-axis noise sources. Microphone assembly 1000 will be better suited for use in vehicles where the person speaking, such as the driver, is not positioned in front of the rearview mirror assembly, because the bi-directional microphone 208 may attenuate the speech from the person speaking. As noted above, the most intense noise in a vehicle originates from the side of the vehicle, which the bi-directional microphone assembly 208 mounted to the mirror assembly 101 will better reject than the hyper cardioid microphone assembly 1000. Another problematic environmental condition better resolved by the bi-directional microphone assembly 208 than the hyper cardioid microphone assembly 1000, is small room reverberation effect. Reverberation causes noise, with a wavelength long relative to room dimensions, such that it is omni-directional. Microphone assembly 208, having two identical transducers, will effectively null omni-directional components, such that all the reverberating noise will be cancelled. The hyper cardioid microphone assembly 1000 will not completely cancel such reverberation noise, due to the differential on-axis sensitivity for the front and rear transducers 1002, 1008.

Whereas bi-directional microphone assembly 208 requires matched transducers such that the noise is cancelled, the hyper cardioid requires transducers producing different on-axis sensitivity. In particular, the transducer sensitivity differential for transducers 1002 and 1008 needs to be 5 to 15 dB, and may for example be 10 dB. The transducer control and damping values, which should be considered for the hyper cardioid microphone assembly 1000, will not be important for the bi-directional polar microphone assembly 208 so long as the transducers are the same. So long as identical transducers are provided, the out of phase and the omni-directional contents, such as mechanical vibration, reverberations, sound having a frequency such that it is non-directional, will null, in microphone assembly 208. The hyper cardioid microphone assembly 1000 requires two different sensitivities from the front and back transducers 1002 and 1008. The transducers must be carefully selected to have the desired sensitivity differential. Microphone assembly 1000 preferably uses higher quality transducers for the front and back transducers 1002, 1008, so that the desired performance can be achieved and sustained, than need be used for the bi-directional microphone assembly 208.

A second order microphone assembly 1100 according to another alternate embodiment is disclosed in FIG. 11. The microphone assembly 1100 includes transducers 1102 and 1112. The front face of transducer 1102 is coupled to a port 1104 through an acoustic channel 1106. The rear face of transducer 1102 is acoustically coupled to port 1110 through channel 1108. The front face of rear transducer 1112 is coupled to port 1110 through channel 1114. The rear face of transducer 1112 is coupled to port 1116 through channel 1118. The transducers 1102 and 1112 are electrically coupled to a circuit 1200 (FIG. 12). The sound from the front transducer 1102 is input to the non-inverting input of an operational amplifier 802. The signal from transducer 1112 is input to a time delay 1202 prior to being input to the amplifier 802. The time delay circuit 1202 introduces a time delay equal to the time period required for sound to travel distance D2, which is the distance from the center of the front transducer 1102 to the center of the rear transducer 1112. The delayed signal is input to the inverting input of the operational amplifier 802 through potentiometer R8.

In operation, the signals originating from the front of the microphone assembly 1100 will reach the rear transducer 1112 a short time period after reaching the front transducer 1102. This time delay is equal to the time required for sound to travel from the center of the front transducer 1102 to the center of the rear transducer 1112. Since the signal entering the rear transducer is electronically delayed in time delay circuit 1202 by an amount equal to the time period required for sound to travel distance D2, the rear signal will arrive at the inverting input of the operational amplifier 802 delayed by a time period equal to twice the time required for sound to travel distance D2. Sound originating from the rear, however will reach front transducer 1102 delayed by a time period equal to the time required for sound to travel distance D2. Because the signal from the rear transducer 1112 signal is delayed electronically, in delay 1202, by a time period equal to the time required for sound to travel distance D2, the signal originating from the back sensed by both transducers 1102 and 1112 will be input to both the non-inverting and inverting inputs of the operational amplifier 802 at the same time, such that they are cancelled by the amplifier 802.

Accordingly, a null is provided for signals originating from the rear of the microphone assembly. It will be recognized that the greater distances D1 and D2 for the second order microphone assembly 1100, the greater the sensitivity of the microphone assembly. Additionally, for every distance D2, there is a crossover frequency above which the difference in phase no longer adds to the output, such that the highest upper frequency desired sets the maximum distance D2. Above the crossover frequency, the microphone will lose its directional properties and suffer frequency response anomalies. It is envisioned that the maximum distance D2 for the second order microphone assembly 1100 will be between 0.75 and 1.4 inches, and may, for example, be approximately 1 inch.

One issue with respect to this implementation, is the phase shift that will occur. In particular, the higher the frequency, the greater the phase shift that the signal will experience between the front transducer and the rear transducer. Low frequency signals will experience little phase shift, whereas high frequency signals will experience a large phase shift. Since acoustic sensitivity increases with additional phase shift, low frequency sensitivity will be very low. However, because the signals of interest are voice signals, which are relatively high frequency signals, the signals of interest will not be significantly affected by this phase shift. Additionally, it is envisioned that equalization techniques can be used to compensate for the phase shift and low frequency roll-off in bass sensitivity of the microphone 1100. The front and back transducers 1102 and 1112 achieve a second order directional function by their spacing. Additionally, the two transducers face the same direction, such that the front face of both the front and rear transducers port forwardly and the back of both the front and rear transducers port rearwardly. The transducers 1102 and 1112 are spaced by a distance D2, which is a dimension close to D1 of the front transducer 1102, and may also be a dimension close to the D3 for the rear transducer 1112. The greatest output from the microphone will occur responsive to on-axis sound in front of the microphone assembly 1100, where the arrival delay is doubled as is the signal strength.

The vibration null and additional acoustic advantages of microphone 208 can be gained for the microphone assemblies 1000 and 1100 by using four transducers, as illustrated in FIG. 11 for microphone assembly 1100. In particular, optional transducers 1120 and 1130 are provided in addition to transducers 1102 and 1112. The rear face of transducer 1120 is coupled to the front port 1122 via channel 1124 and the front face of transducer 1120 is coupled to port 1128 via channel 1126. The front face of rear transducer 1130 is coupled to rear port 1134 via channel 1136 and the back of transducer 1130 is coupled to port 1128 via channel 1132. The front transducers 1102 and 1120 are connected to opposite inputs of the operational amplifier without delay so as to cancel omni-directional noise. The rear transducers 1112 and 1130 are similarly connected to opposite inputs of the operational amplifier, after being delayed by the time period required for sound to travel distance D2, so as to cancel omni-directional noise. Using two pairs of transducers, each pair will achieve a bi-directional pattern and be devoid of vibration noise. In particular, nulls will occur at 90, 180, 270 degrees. The one main lobe of the microphone assembly 1100 is narrow and forwardly directed, being narrower than the bi-directional microphone assembly 208 forward lobe, and having better off-axis noise cancellation.

An automatic balancing circuit 1300 (FIG. 13) can be used in place of, or in addition to, the manual balancing potentiometer R8. Automatic balancing circuit includes a controller 1302 coupled to receive the output of transducer 304 and variable gain amplifier 1304. The controller generates a gain control signal applied to a variable gain amplifier 1304.

In operation, the controller monitors the signal levels output by the transducer 304 and the variable gain amplifier 1304, as indicated in blocks 1402 and 1404 of FIG. 14. The controller monitors for the presence of speech in step 1406. If speech is present, the controller does not adjust the gain of the variable gain amplifier 1304. If speech is not present, the controller determines whether the output of the variable gain amplifier 1304 is equal to the output of transducer 304, in step 1408. If it is not equal, the gain of variable gain amplifier 1304 is adjusted in proportion to the difference between the signal level at the output of transducer 304 and the signal level at the output of amplifier 1304, as indicated in step 1410. The output of the variable gain control will thus be equal to the signal level at the output of transducer 306, thereby providing noise cancellation. Variation in the relative performance of the transducers 304, 306 over time or temperature can thus be compensated automatically by the automatic gain control circuit 1300.

The microphone assemblies 1000 and 1100 can be manufactured in the same manner as the microphone assembly 208, but with different spatial relations for the transducers. For example, whereas the transducers 304 and 306 of microphone assembly 208 are positioned laterally an equal distance from the front and back ports 312, 314, the transducers 1002 and 1008 are positioned one behind the other between the front and back ports 1004, 1010, and may for example be positioned along the longitudinal axis of the microphone assembly 1000, through which the cross section of FIG. 15 is taken.

In particular, the microphone assembly 1000 includes an elastomeric transducer mount 1506 into which transducers 1002, 1008 are mounted. The front of transducer 1002 ports through channel 1005 and the rear of transducer 1008 ports through chamber 1510 and channel 1006. The front face of rear transducer 1008 ports through channel 1011 and the rear surface ports through chamber 1510 and channel 1006. A substantially rigid microphone housing 1512 encloses the transducer mount 1506, and includes mechanical connectors 1504 for connection to the mirror housing 206, as well as bottom, front and rear ports for sound to enter the microphone for passage to the transducers. The connectors 1504 can be snap connectors or connectors that rotate into engagement with the mirror housing in the same manner as connectors 320. The transducer mount 1506 provides acoustic seal with the transducers 1002, 1008, and the circuit board 1502.

FIGS. 16 and 17 show an alternative structure for microphone subassembly 1600. Microphone subassembly 1600, as illustrated, includes an electronic portion 1641, which includes a first microphone transducer 142 and a second microphone transducer 1644 mounted to a printed circuit board 1645.

Microphone transducers 1642 and 1644 may be mounted facing one another or facing away from one another with their central axes aligned coaxially. By mounting microphones 1642 and 1644 to face opposite directions, the sensed pressure waves caused by the vibrations are sensed 180 degrees out of phase from one another. By mounting the microphone subassembly to the vehicle such that the common central axis of the transducers is generally aligned with the driver's mouth, the assembly effectively cancels the noise produced by mechanical vibrations of windshield 20 and the rearview mirror assembly of the vehicle while increasing the gain of the driver's speech. A microphone processor circuit adds the outputs from the two transducers to one another thereby nulling any vibration-induced noise.

As shown in FIG. 17, transducers 1642 and 1644 may be mounted on their sides and the subassembly may include acoustic ports that are 90 degrees relative to the mechanical axes of the transducers. This allows both of the natural transducer front ports to face the redirected front port of the assembly.

According to another embodiment, the inventive microphone assembly utilizes two micro-phone transducers facing in opposite directions. The output of the rear facing transducer preferentially receives noise signals while the output of the forward facing transducer preferentially receives voice signals. Via appropriate electronic processing the presence of significant voice signals can be determined. During periods when there are no significant voice signals, output can be reduced with no harm to voice quality. If this processing is done on a frequency band basis, noise dominated bands can be removed with no harm to voice quality since those bands containing significant voice signals will be passed into the output with no alteration.

Microphone transducers 1642 and 1644 are mounted sideways through holes formed in printed circuit board 1645. Portions of transducers 1642 and 1644 extend below the bottom surface of circuit board 1645 and portions also extend above a top surface of printed circuit board 1645. Mounting the transducers in this orientation and position relative to the circuit board provides several advantages. First, the electrical contacts on the transducers may be directly soldered to traces on the printed circuit board. This avoids the need for manually connecting wires to the transducer contacts and subsequently manually connecting those wires to the circuit board. Thus, the transducers may be mounted to the circuit board using conventional circuit board populating devices.

Another advantage of mounting the transducers such that they extend above and below the surfaces of the printed circuit board is that one side of the circuit board may include a conductive layer serving as a ground plane. Such a ground plane may shield the transducers from electromagnetic interference (EMI) that may be produced by other components within the rearview mirror assembly or in other components within the vehicle. Such EMI can introduce significant noise into the signal delivered by the transducers. In a preferred embodiment, each transducer is mounted in a circuit board having a conductive ground plane facing the acoustically active portion of the transducer while the circuit components are mounted to the opposite side.

As shown in FIGS. 16 and 17, microphone subassembly 1600 further includes an acoustic cup 1650 having a pair of central recesses 1652 and 1654 arranged to accept the portions of microphones 1642 and 1644, respectively, that extend below the bottom surface of printed circuit board 1645. Microphone subassembly 1600 further includes a plurality of ports 1655 disposed about the peripheral bottom portion of acoustic cup 1650. Microphone subassembly 1640 further includes a cloth 1658, which serves as a windscreen and protects the microphones from the external environment. Cloth 1658 is preferably made of a hydrophobic material and is secured to cup 1650 across ports 1665 to keep water from reaching microphones 1642 and 1644.

Microphone subassembly 1600 also includes the outer microphone housing 1660 formed in the shape of a cup with a plurality of acoustic ports 1665 disposed about the bottom and sides of the housing. Ports 1665 are preferably aligned with ports 1655 of acoustic cup 1650. Housing 1660 preferably includes one or more posts 1666 a-1666 c that aligns and mates with grooves 1656 a-1656 c in acoustic cup 1650 and grooves 1646 a-1646 c of printed circuit board 1645. The posts and grooves serve to align ports 1655 and 1665 while also ensuring that the microphone transducers cannot rotate or change orientation within housing 1660. Housing 1660 further includes a plurality of tabs 1662 a-1662 c that resiliently engage the peripheral edge of an aperture formed in mirror housing 206 (FIG. 2). Mirror housing 206 would preferably include corresponding slots for receiving resilient tabs 1662 a-1662 c to ensure that microphones 1642 and 1644 are optimally aligned relative to the vehicle.

While the microphone subassembly is shown in FIG. 2 as being mounted to the bottom of the mirror housing, it should be noted that the preferred location is actually on the top of the mirror housing. An example of a rearview mirror assembly having a microphone subassembly 1600 mounted on the top of the mirror housing is shown in FIGS. 18-20. Microphone subassemblies mounted on a mirror housing receive not only direct sounds from the driver, but also sounds reflected off the windshield. When the microphone subassembly is mounted on the bottom of the mirror housing, there is more of a time difference between the arrival of the direct sound and the reflected sound than when the microphone subassembly is mounted on the top of the mirror housing. When the arrival times are far enough apart, the resulting combination produces a frequency response that has a series of frequencies with no output. The series, when plotted, resembles a comb, and hence is often referred to as the “comb effect.”

Mounting the microphone subassembly on top of the mirror housing avoids the comb effect in the desired pass band. As shown in the side view in FIG. 20, the distance between the windshield and the top of the mirror housing is much smaller than that at the bottom of the mirror housing and thus the reflected sound adds correctly to the direct sound creating a louder, but otherwise unaffected, version of the direct sound. The end result being a higher signal-to-noise ratio and better tonal quality. These are very important attributes in hands-free telephony and vocal recognition in an automotive environment.

A problem with mounting the microphone subassembly to the top of the mirror housing results from the fact that the microphone assembly is closer to the windshield. When the windshield defroster is activated, a sheet of air travels upward along the windshield. Thus, when the microphone subassembly is placed on top of the mirror housing, it is exposed to more airflow as the air from the defroster passes between the mirror housing and the window past the microphone subassembly. This airflow creates turbulence as it passes over the microphone subassembly, which creates a significant amount of noise. To solve this problem, a deflector 1670 extends upward from the rear of mirror housing 1630 so as to smoothly deflect the airflow from the defroster over and/or beside microphone subassembly 1600 so that it does not impact the transducers or create any turbulence as it passes over and around the microphone subassembly. Because the airflow primarily would enter the rear of the microphone subassembly, the deflector may be designed to redirect the air with minimal impact on the frequency response of the microphone subassembly. This is important for high intelligibility in the motor vehicle environment. With no direct air impact and the avoidance of turbulence near the microphone subassembly, mounting the microphone subassembly on the top of the mirror housing can offer superior resistance to airflow-generated noise.

As an additional measure, a signal may be transmitted over the vehicle bus or other discrete wire or wireless communication link, which indicates that the windshield defroster has been activated. This signal could be received and processed by the microphone processor and used to subtract an exemplary noise waveform that corresponds to that detected when the windshield defroster is activated. Alternatively, when the system determines that the driver is speaking into the microphone and that the windshield defroster is activated, the system will temporarily turn down or tarn off the defroster, or otherwise produce a synthesized speech signal advising the driver to turn down the defroster. The voice recognition circuitry within the mirror may also be utilized for purposes of recognizing noise generated by the defroster such that the system will be able to either advise the driver to turn the defroster down or off or to perform that task automatically.

In addition to recognizing the sound produced by the windshield defroster, the microphone may also be used to recognize the sources of various other sounds and hence subtract them from the sound received while the driver is speaking. For example, the microphone may be used to detect low pass response to determine whether the vehicle is moving. Additionally, the microphone may be used to recognize other events, such as a door closing or whether the air bags have been inflated. Upon detecting that the air bags have been inflated, the telematics rearview mirror assembly may be programmed to call 911 and to transmit the vehicle location in a distress signal.

FIG. 21 shows an exploded view of a microphone assembly 1700 constructed in accordance with another embodiment of the present invention. Microphone assembly 1700 includes a pair of transducers 1702 disposed in apertures 1704 at opposite ends of a transducer boot 1706. Transducer boot 1706 includes an inner cavity 1708 by which the front surfaces of transducers 1702 are acoustically coupled and to a forward-facing port 1710 in boot 1706. Transducer boot 1706 is mounted in an aperture 1712 of a circuit board 1714. Thus, a portion of transducer boot 1706 extends below circuit board 1714 while the remaining portion is positioned above circuit board 1714 with port 1710 extending out and resting upon the upper surface of circuit board 1714. An advantage to using a transducer boot 1706 or a similar structure for holding the transducers is that the transducers may be oriented with respect to the transducer boot, inserted into the transducer boot, and held by the transducer boot prior to insertion to the circuit board. Following insertion, the transducer contacts may then be soldered to the circuit board leads. The transducer boot preferably has pegs and other details that facilitate appropriate registration with the circuit board in an auto-insertion apparatus. Thus, rather than requiring the auto-insertion apparatus to somehow grasp a cylindrical transducer and attempt to appropriately align and register the transducer with the circuit board for subsequent soldering, the auto-insertion apparatus would merely need to utilize the details provided in the transducer boot to provide such proper alignment.

Microphone assembly 1700 further includes a boot cover 1720. Boot cover 1720 includes a forward opening 1722 that extends over the protruding port 1710 of transducer boot 1706 so as to allow port 1710 to extend and open outside of boot cover 1720. Boot cover 1720 further includes a pair of tapered side walls 1724 that slope farther apart toward the rear of transducer boot 1720 where a rear opening 1726 is provided. In this manner, an acoustic port is provided at the rear of the microphone assembly, which is acoustically coupled via the tapered side walls 1724 to the rear surfaces of transducers 1702.

Microphone assembly 1700 further includes a windscreen 1730, which is preferably a hydrophobic and heat-sensitive adhesive-coated fabric. Windscreen 1730 is adhesively attached to the underside of a microphone assembly cover 1732 so as to extend across ports 1734 provided in cover 1732. Cover 1732 is preferably tightly bonded about circuit board 1714 to provide a water-impervious enclosure for transducers 1702.

Microphone cover 1732 is shown in FIG. 21 as having a generally square shape. It should be noted, however, that cover 1732 may be a rectangle or other shape and the size and shape of apertures 1734 may be changed so as to adjust the directionality of the microphone. Further, the acoustic resistivity of windscreen 1730 may be varied to also vary the directionality and polarity of the microphone assembly. Specifically, the acoustic resistivity of windscreen 1730 may be increased to at least about 1 acoustic Ω/cm² and preferably has an acoustic resistivity of at least about 2 acoustic Ω/cm².

To illustrate the effect of adjusting the acoustic resistivity of the windscreen and the size and positioning of the ports in the microphone housing cover, the polar patterns were plotted for the microphone assembly with and without the cover and windscreen surrounding the microphone transducers at four different frequencies, which are plotted in FIGS. 22A-22D and in FIGS. 23A-23D. The polar patterns (FIGS. 22A-22D) were plotted with the cover and windscreen in place, and then, the cover and windscreen were removed and the polar patterns were plotted for the same four frequencies, which are shown in FIGS. 23A-23D. Specifically, the polar patterns shown in FIGS. 22A and 23A show the microphone characteristics at 250 Hz, the polar patterns shown in FIGS. 22B and 23B were taken at 500 Hz, the polar patterns shown in FIGS. 22C and 23C were taken at 1000 Hz, and the polar patterns shown in FIGS. 22D and 23D were taken at 2000 Hz. As apparent from a comparison of the respective polar patterns, the rear lobe that is present when the cover is not provided over the transducers is effectively eliminated by appropriately configuring the cover and windscreen.

While it has been typical in conventional microphones to minimize the acoustic resistivity of a windscreen by increasing the porosity of the windscreen, the microphone assembly of the present invention advantageously utilizes a windscreen with a higher acoustic resistivity by decreasing the porosity of windscreen and yet obtaining not only better water-resistant properties, but to also improved the acoustic characteristics for the microphone assembly. The reduction of the rear lobe of the polar pattern of the microphone assembly is particular advantageous when the microphone assembly is mounted on a rearview mirror assembly since significant noise may be introduced from the windshield defroster where such noise is typically to the rear and sides of the microphone assembly.

When the microphone transducers are sealed in separate housings having their own cover and windscreens, the cover ports and acoustic resistivity of the windscreens may be different for the different transducers so as to compensate for any effects experienced by the transducers as a result of the positioning of the transducers on the vehicle accessory. For example, when one transducer is mounted closer to the face of the rearview mirror, its polar pattern is different from that of a transducer spaced farther from the mirror surface. Thus, by selecting an appropriate cover design and windscreen resistivity, the effects of the differences resulting from the positioning of the transducers may be compensated such that the transducers exhibit substantially similar polar patterns and other characteristics. While the windscreen has been described above as consisting of a hydrophobic fabric, it will be appreciated that the windscreen may be molded integrally across the ports of the microphone assembly cover. Such an arrangement would simplify the manufacturing of the microphone assembly by requiring less parts and less manufacturing steps. Further, it would more likely provide a more effective seal between the windscreen and the cover.

FIG. 24 shows yet another embodiment of a microphone assembly 2000. As illustrated, microphone assembly 2000 is positioned on the top of a rearview mirror assembly mirror housing 1630 in a manner similar to that shown in FIGS. 18-20. Similar to that embodiment, a deflector 1670 is provided that extends from the upper rear portion of mirror housing 1630 so as to provide a relatively flat surface 2005 on which the microphone assembly 2000 may be mounted.

Microphone assembly 2000 includes two separate microphone housings. A first microphone housing 2002 is positioned forward of a second microphone housing 2004 and is positioned closer to the face of the rearview mirror assembly and hence closer to the driver of the vehicle. First microphone housing 2002 includes a cover 2012 having a plurality of ports 2008 through which sound may pass. Second microphone housing 2004 likewise may include a cover 2014 having a plurality of acoustic ports 2010. Both housings preferably include a windscreen similar to that discussed above. The configuration of the ports on the covers and the acoustic resistivity of the windscreens may be different for each of housings 2002 and 2004 so as to compensate for any effects caused by the positioning of the transducers on the rearview mirror assembly.

Each of microphone housings 2002 and 2004 preferably include a single transducer having its front surface facing the driver of the vehicle. As shown in FIG. 25, the central axes of the transducers and covers 2012 and 2014 may be aligned along a common axis that is at an angle .theta. relative to a perpendicular bisector (i.e., normal) to the rearview mirror surface. This is to ensure the transducers are coaxially aligned with the driver's mouth, since the rearview mirror surface would be at more of an angle to allow viewing through the rear window of the vehicle. It should be noted that the transducers need not be aligned coaxially, but may be skewed with respect to one another. Such an embodiment is described further below.

As also discussed further below, microphone assembly 2000 is preferably a second order microphone assembly with the centers of the two transducers physically separated by between about 0.75 and 1.4 inches, and preferably between about 1.0 to 1.3 inches. By spacing the transducers 1.3 inches apart, the distance between the transducers is approximately one-half the wavelength of sound at 5 kHz. The two transducers may be housed in the separate microphone housings discussed above. In the presently preferred embodiment, the transducers are identical and are spaced 1.0 inch apart. The front transducer should preferably be as far forward as possible, and most preferably should be about 0.25 inch from the front glass surface of the mirror.

According to an embodiment of the present invention, the transducer in each housing is ported so as to effectively be aimed down the center of the vehicle rather than directly at the driver's mouth. By aiming the transducers down the center of the vehicle, the transducers are still able to clearly pick up the driver's voice, but do not pick up nearly as much of the considerable noise that originates to the side of the vehicle by the driver. In a typical vehicle, the mirror is correctly positioned for a typical driver when it is positioned between about 14 and 22 degrees relative to the horizontal axis of the vehicle (i.e., a horizontal axis of the vehicle is one that is parallel to the horizontal axes of vehicle's axles). For purposes of the invention, an assumption of 20 degrees is made so that the transducers are generally aligned along a line that is 20 degrees from a line that is perpendicular to the mirror surface in the direction away from the driver. This results in the transducers generally being aligned with a line down the center of the vehicle. It is also beneficial to slightly turn the front transducer further away from the driver such that it is no longer coaxial with the rear transducer.

To attempt to obtain a required sensitivity accuracy for the transducers, a laser trim tab may be added to the gain stage connected to each transducer. The transducers may then be acoustically excited by a calibrated sound source and the output of the transducers is monitored. The laser trim tab is then trimmed to precisely set the gain and thereby obtain precise sensitivity accuracy.

Because of the frequency response of components in existing telephone networks, it may be beneficial to increase the separation distance between the transducers to between 1.7 and 1.9 inches. Because space may be limited on the accessory surface on which the transducers are mounted, it may not be possible to physically separate the transducers by such a distance. To overcome this problem, a mechanical structure 2006 may be disposed between the first transducer and the second transducer to increase the acoustic path length between the first and second transducers. Mechanical structure 2006 may have any symmetrical conical structure and is shown in FIG. 25 as having the shape of a pyramid. As apparent from FIG. 24, any on-axis sound passing by the first housing 2002 towards the second microphone housing 2004 must pass up and over mechanical structure 2006. On the other hand, any sound coming off-axis from the sides will still be received at the same time by both microphone structures 2002 and 2004 regardless of the presence of mechanical structure 2006. Test results have shown that a pyramid-shaped mechanical structure 2006 having a height of 0.35 inch and side dimensions of 0.70 inch with a 45-degree incline of the side surfaces toward the peak that the acoustic path length may be increased by approximately 0.35 inch. Thus, greater acoustic separation of the two transducers may be obtained without having to physically separate the transducers by a greater distance. This enables the structure to be mounted on relatively small surfaces.

It should be noted that an additional common cover for the microphone assembly 2000 shown in FIGS. 24-26 may be secured over the illustrated structure provided that the common housing is substantially acoustically transparent so as to not affect the arrival times of the sound to the two transducers.

As shown in FIGS. 24 and 26, a surface of deflector 1670 may include a structure designated as 2020 that is hereinafter referred to as a “fine turbulence generator.” Fine turbulence generator 2020 may be implemented using a fabric or other fine structure so as to create fine turbulence between deflector 1670 and the laminar airflow along the windshield defroster as it passes over deflector 1670. A preferred fine turbulence deflector may be implemented using the loop portion of a hook-and-loop-type fastener such as the VELCRO hook-and-loop fastener. Alternatively, the corresponding surface of deflector 1670 may simply be roughened to create similar turbulence.

While turbulence generally is undesirable due to the noise it produces, creating very fine turbulence in the manner proposed creates turbulence having frequency components that exceed the audible limits of humans while reducing the turbulence of the air passing by deflector 1670 that would produce lower frequency components within the audible limits of humans. Because of the fine turbulence created along the surface of deflector 1670, the laminar airflow is deflected by the fine turbulence that is created rather than the deflector itself. This reduces the friction of the deflector as seen by the laminar airflow and therefore reduces the turbulence created by the airflow that would otherwise tend to create lower frequency noise within the audible frequencies.

Due to the large size of the mirror surface and the proximity of the forward most transducer to the mirror surface, the polar patterns of the two transducers may vary from one another on a frequency dependent basis. In some applications, it may be desirable to include second transducers in each of the two microphone housings to alter the polar pattern over a frequency range, and thereby compensate for this discrepancy. By utilizing these additional transducers and utilizing additive signals to correct the polar with regard to frequency, nearly identical and optimum cardioid polar responses may be attained over the entire desired pass band. According to one embodiment of the present invention, the second transducer in the front microphone housing may be an omni-directional transducer while the second transducer in the rear microphone housing may be a cardioid transducer.

FIG. 27 shows a block diagram of a microphone processing circuit 2100 that may be used with the second order microphone assembly 2000 as depicted in FIGS. 24-26. It will be appreciated, however, that microphone processing circuit 2100 may be used with any second order microphone assembly regardless of whether it is incorporated in a rearview mirror assembly, in another vehicle accessory, or in any other audio application outside of the vehicle environment.

Circuit 2100 includes a front transducer 2102 and a rear transducer 2104. As discussed above, for a second order microphone assembly, front and rear transducers are preferably disposed with their front surfaces facing the direction of the person speaking. The output 2104 a of rear transducer 2104 is coupled to the input 2106 a of a high pass filter 2106. The output of high pass filter 2106 b is coupled to a first input 2108 a of a summing circuit 2108.

The output 2102 a of front transducer 2102 is coupled to the input of 2110 a of an all-pass phase shifter 2110. The output of all-pass phase shifter 2110 b is coupled to an inverting input 2108 b of summing circuit 2108. As discussed further below, phase shifter 2110 is provided to shift the phase of the signal from front transducer 2102 by an amount equivalent to the phase shift inherent in high-pass filter 2106 such that the signals from front and rear transducers 2102 and 2104 have their phase shifted by equal amounts prior to application to summing circuit 2108 where the signal from front transducer 2102 is inverted and summed with the filtered signal from rear transducer 2104 (i.e., the signals are effectively subtracted). The output 2108 c of summing circuit 2108 is coupled to the input 2112 a of a three-pole high-pass filter 2112. The output 2112 b of three-pole high-pass filter 2112 may be coupled to the input 2114 a of an optional buffer circuit 2114. The output 2114 b of buffer circuit 2114 represents the output of the inventive microphone processing circuit.

Microphone processing circuit 2100 as shown in FIG. 27, includes a biasing circuit 2116, which produces a bias voltage V_(B) that is applied to each of components 2106-2114, as more apparent from the schematic representations of each of those components. Biasing circuit 2116 includes a pair of series-connected resistors 2118 and 2120 coupled between a supply voltage V_(S) and ground. Resistors 2118 and 2120 preferably have a resistance of 10 k/Ω. Biasing circuit 2116 further includes a capacitor 2122 coupled between the output of biasing circuit 2116 and ground. Capacitor 2122 preferably has a capacitance of 2.2 μf.

The details of components 2106-2114 are shown schematically in FIGS. 28A-28E, and are discussed in further detail below following a description of the general circuit operation.

To understand the performance and advantages of the inventive microphone processing circuit 2100, it is first necessary to understand the operation of a conventional circuit used with second order microphone assemblies. In prior second-order microphone processing circuits, the output of the front transducer was simply inverted and provided to a summing circuit where the signal was summed with the signal directly supplied from the rear transducer. The frequency response of such a processing circuit is shown in FIG. 29A. In FIG. 29A, plot A shows the sensitivity of the second order microphone assembly at various frequencies with the sound originating on-axis. Plot B shows the microphone sensitivity at various frequencies with the sound originating 180 degrees from the axes (i.e., from behind the microphone assembly). Plot C shows the microphone sensitivity for various frequencies arriving at an angle 90 degrees from the central axes of the transducers (i.e., directly from the side of the microphone assembly). As apparent from FIG. 29A, such a microphone circuit is very sensitive to higher frequencies, but is not very sensitive to lower frequencies within the audible band for those sounds originating on-axis. To compensate for the low frequency sensitivity, a high-pass filter may be added at the output of the summing circuit. While such an arrangement serves to provide a more uniform sensitivity across the frequencies in the audible range, the introduction of the filter renders the assembly extremely sensitive to vibration-induced noise. More specifically, torsional vibration of the transducers is amplified using such a configuration.

To overcome these problems, the inventive microphone processing circuit utilizes a high-pass filter 2106 between one of the transducers and summing circuit 2108. High-pass filter 2106 could be placed at the output of either front transducer 2102 or rear transducer 2104. High-pass filter 2106 preferably has a characteristic cut-off frequency at about 1 kHz. By filtering the output of one of the transducers to reduce its bass frequency components prior to subtraction from the other transducer output, the bass of the resultant output is reduced by a smaller amount than it otherwise would in the absence of filter 2106. As discussed above, all-pass phase shifter 2110 is provided in the path of the other transducer so as to ensure that the phase of the signals from front and rear transducer 2102 and 2104 are shifted by the same amount prior to reaching summing circuit 2108. FIG. 29B illustrates the frequency response of the system when phase shifter 2110 is not utilized. As apparent from FIG. 29B, there is a steep drop off in response at the middle of the audible range, which results from the phase difference of the signals that would otherwise be applied to summing circuit 2108.

FIG. 29C shows the frequency response of the inventive microphone processing circuit 2100 having the construction shown generally in FIG. 27 and specifically in FIGS. 28A-28E and described further below. As apparent from FIG. 29C, the sensitivity of the microphone assembly to on-axis sound is relatively uniform across the audible range. The on-axis sensitivity is referenced in FIG. 29 as plot A. The 180-degree off-axis sound sensitivity is designated in FIG. 29C as plot B. Plot C represents the microphone assembly sensitivity to sound arriving off-axis at 145 degrees while plot D represents sound originating from a point 90 degrees off-axis. As apparent from a comparison of these plots, the second order microphone assembly of the present invention is significantly more sensitive to on-axis sound while is clearly less sensitive to off-axis sound, particularly at lower frequencies. As noted above, in an automobile environment, most the noise arrives off-axis towards the sides of the microphone assembly. Thus, the above described second order microphone assembly 2000 and circuitry 2100 is significantly less sensitive to noise originating from those directions.

FIG. 28A is a schematic diagram showing the preferred construction for high-pass filter 2106. High pass filter 2106 includes a first resistor 2124, preferably having a resistance of 8.2 k/Ω, which is coupled between filter input 2106 a and supply voltage V_(S). A capacitor 2126, preferably having a capacitance of 0.001 μf, is coupled between input 2106 a and ground. High-pass filter 2106 also includes an operational amplifier 2128, preferably part No. LM2904, having its non-inverting input terminal coupled to bias voltage V_(B), and its inverting input coupled to input terminal 2106 a via series-connected capacitor 2130 and resistor 2132. Capacitor 2130 preferably is a 0.01 μf capacitor while resistor 2132 preferably has a resistance of 10 k/Ω. High-pass filter 2106 also preferably includes a feedback resistor 2134 coupled between the inverting input and the output of amplifier 2128. Another resistor 2136 is coupled between the output of amplifier 2128 and ground. Preferably, resistors 2134 and 2136 both have a resistance of 10 k/Ω. The output of amplifier 2128 serves as the output 2106 b of high-pass filter 2106.

FIG. 28B shows the preferred construction of all-pass phase shifter 2110. Phase shifter 2110 includes a first resistor 2138 that is coupled between input terminal 2110 a and supply voltage V_(S). Resistor 2138 preferably has a resistance of 8.2 k/Ω. A capacitor 2140, preferably having a capacitance of 0.001 μf, is coupled between input terminal 2110 a and ground. A capacitor 2142 and a resistor 2144 are coupled in series between input terminal 2110 a and an inverting input of an amplifier 2146. Capacitor 2142 preferably has a capacitance of 1 μf. A feedback resistor 2148 is coupled between the inverting input and the output of amplifier 2146. A resistor 2150 is coupled between the output of amplifier 2146 and ground. Amplifier 2146 is preferably part No. LM2904. Another resistor 2152 is coupled between the non-inverting input of amplifier 2146 and biasing circuit 2116. A capacitor 2154 is coupled between the non-inverting input of amplifier 2146 and a terminal between capacitor 2142 and resistor 2144. Capacitor 2154 preferably has a capacitance of 0.01 μf. Resistors 2144, 2148, 2150, and 2152 all preferably have resistances of 10 k/Ω. The output of amplifier 2146 serves as the output 2110 b of phase shifter 2110.

FIG. 28C shows a preferred construction for summing circuit 2108. Summing circuit 2108 includes an amplifier 2156 having its non-inverting input coupled to biasing circuit 2116 so as to receive a bias voltage V_(B). Input terminal 2108 a is coupled to the inverting input of amplifier 2156 via series-connected capacitor 2158 and resistor 2160. Similarly, input terminal 2108 b is coupled to the inverting input of amplifier 2156 via series-connected capacitor 2162 and resistor 2164. Capacitors 2158 and 2162 preferably have a capacitance of 1 μf. A resistor 2166 is coupled between the inverting input and the output of amplifier 2156. A resistor 2168 is preferably coupled between the output of amplifier 2156 and ground. Resistors 2160, 2164, and 2168 all preferably have a resistance of 10 k/Ω while resistor 2166 has a resistance of 100 k/Ω. Amplifier 2156 is preferably part No. LM2904. The output of amplifier 2156 serves as the output 2108 c from summing circuit 2108.

FIG. 28D illustrates a preferred construction for three-pole high-pass filter 2112. Bypass filter 2112 preferably includes an amplifier 2170 and three capacitors 2172, 2174, and 2176 coupled in series between input 2112 a and the non-inverting input of amplifier 2170. Capacitors 2172, 2174, and 2176 preferably have capacitances of 0.33 μf. A resistor 2178 is coupled between ground and a terminal between capacitors 2172 and 2174, a resistor 2180 is coupled between the inverting input of amplifier 2170 and a terminal between capacitors 2174 and 2176, and a resistor 2182 is coupled between the non-inverting input of amplifier 2170 and bias circuit 2116. A resistor 2184 is coupled between the output of amplifier 2170 and ground. The inverting input and output of amplifier 2170 are electrically coupled. Resistor 2178 preferably has a resistance of 6.8 k/Ω, resistor 2180 preferably has a resistance of 1.1 k/Ω, resistor 2182 preferably has a resistance of 270 k/Ω, and resistor 2182 preferably has a resistance of 10 k/Ω. Amplifier 2170 is preferably part No. LM2904. The output of amplifier 2170 serves as the output 2112 b of filter 2112. Having this construction, the cut-off frequency of this high-pass filter is about 300 Hz. It should be noted that a different cut-off frequency could be utilized in microphone processing circuit 2100.

FIG. 28E illustrates a preferred construction for buffer circuit 2114. Buffer circuit 2114 preferably includes an amplifier 2186 having its non-inverting input coupled to input terminal 2114 a via a capacitor 2188. A resistor 2190 is coupled between the non-inverting input of amplifier 2186 and bias circuit 2116. The inverting input of amplifier 2186 is coupled to ground via series-connected resistor 2192 and capacitor 2194. A resistor 2196 is coupled between the inverting input and the output of amplifier 2186. A resistor 2198 is coupled between the output of amplifier 2186 and ground. A capacitor 2199 is coupled between the output of amplifier 2186 and the output 2114 b of buffer circuit 2114.

While the specific circuit implementation is described above for microphone processing circuit 2100, it will be appreciated by those skilled in the art that other configurations may be utilized without departing from the scope of the invention.

In some applications, it may be desirable to purposely boost the gain of the transducers in certain frequency ranges to compensate for the effect of the vehicle on the frequency response that is output from the microphone assembly. For example, a microphone assembly was constructed having a generally flat frequency response curve up to 5 kHz. However, when this microphone assembly was placed in certain vehicles, the frequency response was flat only to about 3.5 kHz and dropped off somewhat significantly between 3.5 and 5 kHz. Thus, to compensate for the effect the vehicle had on the microphone assembly output, the frequency band between 3.5 and 5 kHz was purposely boosted to give the microphone assembly a non-flat response curve to thereby compensate for these effects and to provide a flat output signal up to 5 kHz from the microphone assembly. Such a flat output up to 5 kHz is generally desired when utilizing voice recognition processing.

FIG. 30 shows an alternative microphone processing circuit that utilizes a digital signal processor (DSP).

As shown in FIG. 30, the microphone assembly may include one or more transducers 2210. The microphone processing circuit of the microphone assembly includes a DSP 2220 and may optionally include a pre-processing circuit 2215 disposed between an input to DSP 2220 and an output of transducer(s) 2210. Alternatively, DSP 2220 could be coupled between pre-processing circuit 2215 and transducer(s) 2210. The output of DSP 2220 may be applied to various devices such as a voice recognition device, a recording device, or to a transceiver of a radio or cellular telephone.

DSP 2220 may be any appropriately configured DSP, but is preferably either of part nos. TMS320VC5×5409 or 5402 available from Texas Instruments. The microphone may, but need not necessarily, include two or more transducers arranged as disclosed above, while a corresponding pre-processing circuit such as those disclosed above may also be used for circuit 2215. By using two transducers with one spaced farther away from the person speaking, the arrival time of sounds picked up by the transducers may be used to determine the likely source of the sounds. For example, the transducer closest to the person speaking will detect a sound originating from that person before the furthest transducer. Conversely, any sound that is first detected by the furthest transducer may be identified as noise. Likewise, any sounds arriving off-axis and received by both transducers at the same time may also be discarded as noise.

Human vocal cords resonate and thereby create a single frequency with overtones (also known as harmonics). All vocal cord energy is therefore confined to the harmonics of the vocal cord fundamental frequency. For a human male, the fundamental frequency is typically between 35 and 120 Hz, and for a female, the fundamental frequency is typically between 85 and 350 Hz. The DSP filter 2220 of the present invention identifies the fundamental frequency of the speech signals received by transducer(s) 2210 and use the identified fundamental frequency to compute the coefficients for an inverse comb filter that will pass only the harmonics of the vocal cords of the person(s) whose speech signals are received. In contrast to conventional noise filters that try to identify the noise, the inventive filter identifies the speech. The inventive filter may also be used to separate one talking person from another as long as both have different fundamental frequencies.

FIG. 31 shows a process diagram for the adaptive filter as implemented in DSP 2220. As depicted in block 2225, the analog audio signal from transducer(s) 2210 is converted into a digital audio signal. A fast Fourier transform (FFT) is then performed on the digitized audio signal as shown in block 2230. An example of an FFT of an audio signal including a speech signal and noise is shown in FIG. 32. Using the FFT of the digitized audio signal, the fundamental frequency of the speech signal is determined as depicted in block 2235. DSP 2220 identifies the fundamental frequency by identifying frequency components in the FFT that have amplitudes exceeding a predetermined threshold, and then identifying the fundamental frequency as the difference in frequency of those frequency components having an amplitude above the predetermined threshold. As apparent from the exemplary FFT shown in FIG. 32, the highest peaks are separated by an amount equal to the fundamental frequency f₀ and appear at frequencies that are at multiples of the fundamental frequency. Those peaks in the FFT correspond to the harmonic frequency components of a person's speech.

After the fundamental frequency is determined in block 2235, adaptive filter coefficients are generated (block 2240) and used to configure an inverse comb filter (block 2245) that is used to filter the digitized audio signal supplied by transducer(s) 2210. An example of an inverse comb filter characteristic is shown in FIG. 33 that is suitable for filtering a signal having the FFT shown in FIG. 32. The filtered digital signal may then be converted to an analog speech signal as depicted in block 2250. For a discussion of how an inverse comb filter may be configured in a DSP, see Digital Signal Processing Primer, by Ken Steiglitz, 1996, ISBN 0-8053-1684-1.

As shown in FIG. 33, the inverse comb filter passes all frequency components above a predetermined frequency, such as 2500 Hz. This may be desirable because certain higher frequency sounds in human speech such as “S,” “Sh,” “T,” and “P” sounds, may not be at a harmonic frequency of the vocal cords. In a vehicle environment where much of the noise is at lower frequencies, passing all higher frequency components typically does not present a problem. As described further below, DSP 2220 may be configured to predict and hence separate such “S,” “Sh,” “T,” and “P” sounds in human speech from noise at those higher frequencies. Filtering, such as spectral subtraction, can be employed in the region above the inverted comb filtering frequencies to reduce noise in this band.

By continuously monitoring the incoming audio signal for any changes in the fundamental frequency, DSP 2220 may adjust the filter coefficients in response to any detected change in the fundamental frequency. The manner in which DSP 2220 adjusts filter components may be pre-configured to prevent abrupt changes that may occur when, for example, another occupant of the vehicle begins speaking. The desired frequency response of the person speaking may thus be estimated and maintained. Consistency in response is an important factor in speech recognition. This adjustment is made by comparing the relative intensity of the harmonics over the reference time interval. This relationship will then be maintained. For example, in the first few utterances, the second average harmonic peak value may be 3 dB greater than that of the third. If this relationship drifts, the original value will be restored. This concept can also be applied to the relative intensity of the sibilance utterances and the vocal cord levels. The resulting speech output may not exactly reproduce a person's normal tonality, but it will reproduce a consistent one. Combined with output level, this adjustment should help vocal recognition by removing two very important variables.

It should also be noted that DSP 2220 may configure two or more superimposed inverse comb filters each corresponding to the harmonics of different individuals in the vehicle. The system may also be taught to default to the fundamental frequency most often, or last, identified upon being activated so as to limit any delay caused by the subsequent identification of the fundamental frequency.

Blocks 2255 and 2260 of FIG. 31 illustrate an inventive variable gain adjustment that may optionally be implemented in DSP 2220. The gain of the filtered digitized signal may be varied (block 2255) prior to conversion into an analog signal. The amount that the gain is varied is a function of the noise level detected in the digitized audio signal received from transducer(s) 2210 corresponding to a polar pattern with a null facing the direction of the driver, preferably a cardioid or super cardioid.

A second configuration for DSP 2220 is shown in FIG. 34. According to the second configuration, two transducers are used each having a polar pattern corresponding to a super-cardioid. The first transducer 2302 is directed on axis towards the person speaking (typically the driver in an automotive environment), while the second transducer 2304 is positioned in the opposite direction with a null in the polar facing the person speaking. In this manner, while first transducer 2302 will pick-up the person's speech as well as some noise, second transducer 2304 will not pick-up the person's speech, but will only pick up noise including much of the same noise picked-up by first transducer 2302. Thus, the output signal of second transducer 2304 may be subtracted from that of first transducer 2302 to remove unwanted noise. Second transducer 2304 may alternatively haven an omni-directional polar pattern.

The diagram in FIG. 34 shows that the audio signal of first transducer 2302 is converted into a digital audio signal (block 2306) and that the audio signal of second transducer 2304 is also converted into a digital audio signal (block 2308). The digitized audio signals from both transducers are processed to detect the presence of speech (block 2310) and are also both compared to one another (block 2312). In response to the comparison of the signals from first and second transducers 2302 and 2304, the gain/phase of the signal from transducer 2304 is selectively adjusted (block 2314). The gain/phase adjusted signal from second transducer 2304 is inverted (block 2316) and is summed with the digitized signal from first transducer 2302 (block 2318). The resultant summed signal may optionally be converted into an analog signal (block 2320). Because the summed signal actually corresponds to the subtraction of an adjusted audio signal from second transducer 2304 from that first transducer, the summed signal should represent the speech (if present) with any noise removed. When speech is not present, however, the summed signal should be a null. Speech may be detected by performing a FFT on the received audio signal and looking from a fundamental frequency in the range of that expected for a human.

To appropriately adjust the gain/phase of the signal from second transducer 2304, the detection of the presence of speech (block 2310) may be used in the determination of the appropriate gain/phase adjustment to be made. Further, nulls may be detected in the summed signal (block 2322) for use in adjusting the gain/phase of the signal from second transducer 2304.

As shown in FIG. 34, some phase adjustment (block 2324) may be desired to introduce a phase delay into the audio signal from first transducer 2302 that corresponds to that inherently introduced during inversion (block 2316) of the audio signal from second transducer 2304.

The system in FIG. 34 may be configured to adjust the gain of the signal only when speech is detected to ensure that the gain is not suddenly boosted during periods between speech and thereby avoid boosting the noise level during those periods. This configuration overcomes the problems typically associated with using automatic gain control in which the gain is automatically increased during periods between speech and thereby unnecessarily amplifying noise.

It should be noted that both the functions outlined in FIGS. 31 and 34 may be combined in whole or in part to achieve various significant improvements in speech processing.

The present invention also may use the time relationship between vocal cord events and sibilance occurrences to identify the spoken phoneme and recreate it correctly. This may add processing delay but significantly improves vocal recognition. Knowing when the vocal event occurred, the system can look for minor differences relative to the preceding time interval. There are a limited number of possibilities and due to noise, nature can be recreated more universally than the more unique vocal cord noises. For example, the system can determine that a “Sh” sound was uttered and recreate a perfect “Sh” sound. Other utterances include the “S,” “T,” and “P” sounds. These are all simple noise bursts of well defined nature.

The environment around separated transducers significantly disturbs the frequency response and polar of each transducer. For example, a transducer located closer to the front surface of a mirror in a rearview mirror assembly will experience a different polar and frequency response than a transducer located farther back. The inventive system can combine acoustic adjustments and adaptive adjustment to compensate for these errors. The transducer balance may be adjusted on an adaptive band by band basis to minimize the dominant acoustic noise in each band. This assures the greatest noise reduction possible. Such an adjustment is preferably performed only during the intervals between speech utterances. Any resulting reduction in speech level will be compensated automatically. Noise reduction will be greater than any speech level loss. This assures a maximum signal-to-noise ratio.

Typically, the only controlled analog aspect in complex audio systems employing a DSP is gain control. In most other ways, the microphone and its analog characteristics have been assumed to have predetermined characteristics and the resulting DSP application is developed around the microphone's predetermined frequency response. The end result is a situation where the microphone must have the same frequency response as the one upon which the design was based in order to function correctly. This situation prevents changing the microphone frequency response, which potentially would provide other advantages.

A very important advantage can be achieved by reducing the analog sensitivity in frequency bands that are dominated by noise. If gain control is provided, the highest input signal typically sets the gain level. If dynamic gain control is not provided, the system gain is typically set at a fixed level corresponding to the highest expected input signal. In a system having gain control, when noise is dominant, the noise sets the gain level. This action effectively prevents the gain from being set correctly for best speech entry.

If the noise present creates signals having amplitudes larger than that of speech signals, the possibility exists that the noise generated signals will cause clipping in the analog stages resulting in gross distortion aid very large spurious noise artifacts.

The present invention addresses the above issues using two different approaches. According to the first approach, the desired microphone/analog response is created and an offset table from the initial design frequency response is created. This table is used by the DSP software to correct the digitized data creating values the designed microphone would have yielded in the same conditions. In other words, the DSP software need not be modified for the system to utilize a microphone having a frequency response different from that for which the DSP software was designed. The offset table is provided to provide a microphone frequency response that the DSP would expect from the design microphone despite the fact that the microphone being used has a different frequency response. This allows for the use of a microphone having a frequency response that is more suitable for certain applications such as applications where voice recognition is used. Since this approach would occur in the first processes performed by the DSP, usually an FFT, no concern would be present about the effect on the software that currently limits microphone frequency response flexibility.

The first approach discussed above assumes a fixed frequency response different from the designed-around response. A more powerful use, one requiring appropriate DSP software, would be adaptive. In this form, the DSP software can dynamically control the analog frequency response. The DSP software could, for example, determine that noise is dominant in a given frequency band and then attenuate signals within that frequency band. The DSP software could also determine if speech was dominant but deficient in a particular frequency band and increase the gain for that frequency band. Since the DSP software would know the impact of this action, it could then compensate by post-digitization processing.

Utilizing such dynamic and adaptive control of the analog frequency response assures the full dynamic range of the analog portion, especially the CODEC, would be used for speech processing. A gross difference in signal content between frequency bands could be eliminated assuring all speech sound bands are present in the resulting data. Since some noise, such as wind flutter, is not easily discernable from speech, there might be some degree of assumed noise. This would mean the bass response would generally be more curtailed than other bands.

In general terms, the above two approaches seek to optimize the analog frequency response while preserving the advantage of iterative design in which the characteristics of the microphone are too engrained to be directly changed without unforeseen consequences.

According to another aspect of the present invention, reliable continuity is provided through a two wire microphone interface that removably couples a microphone assembly to an electronic assembly. The microphone assembly includes a power source and a two wire microphone interface. The microphone interface includes two contacts that provide an audio signal to the electronic assembly. A continuous direct current is provided through the two contacts such that a low impedance path is maintained between the microphone assembly and the electronic assembly.

FIG. 35 depicts a simplified electrical schematic of a microphone assembly (including a prior art microphone interface) 2400 coupled to an electronic assembly 2402 (e.g., a differential amplifier stage). As shown in the circuit of FIG. 35, power is provided to the microphone 2400 via a power source (VAUDIO). VAUDIO is coupled to a first end of a resistor R5. A second end of resistor R5 is coupled to a contact 2 of a connector J1. When mated, contact 2 of connector J1 is coupled to a contact 4 of connector J1 and to a first end of a resistor R6. A second end of resistor R6 is coupled to a first end of a resistor R14. A second end of resistor R14 is coupled to a contact 3 of connector J1. Contact 3 of connector J1 is coupled to a contact 1 of connector J1, which is coupled to a first end of a resistor R11. A second end of resistor R11 is coupled to a common ground of the electronic assembly 2402.

In brief, VAUDIO provides power to the microphone assembly via a resistor R5. The current through resistors R5 and R6 provides a charging current to capacitor C4, which serves to provide a filtered microphone power supply (VMIC). A continuous wetting current (DC) is provided by VAUDIO through resistor R5, contacts 2 and 4 of connector J1, resistors R6 and R14, contacts 3 and 1 of connector J1 and resistor R11. Transistor Q1, which is coupled to the first end of resistor R6 and the second end of resistor R14, represents the load presented by a microphone preamplifier.

Turning to FIG. 36, a simplified electrical schematic of a microphone assembly 2500 (including a microphone interface, according to an embodiment of the present invention) coupled to an electronic assembly 2502 (e.g., a differential amplifier stage) is shown. VAUDIO is coupled to a first end of a resistor R5. A second end of resistor R5 is coupled to a first end of a resistor R6. A second end of resistor R6 is coupled to a contact 2 of a connector J1. When mated, contact 2 of connector J1 is coupled to a contact 4 of connector J1 and a first end of a resistor R12. A second end of resistor R12 is coupled to a first end of a resistor R8. A second end of resistor R8 is coupled to a first end of a resistor R13. A second end of resistor R13 is coupled to a contact 3 of connector J1, which is coupled to contact 1 of connector J1. Contact 1 of connector J1 is coupled to a first end of a resistor R11. A second end of resistor R11 is coupled to a common ground of the electronic assembly 2502.

As shown in FIG. 36, while an auxiliary power supply (V1) provides power to the microphone assembly 2500 (or at least a portion of microphone assembly 2500), the wetting current (DC) is supplied by the electronic assembly 2502 power source VAUDIO. The wetting current (DC) is supplied from VAUDIO through resistors R5 and R6, contacts 2 and 4 of connector J1, resistors R12, R8, R13 and resistor R11. The microphone interface, according to the present invention, provides a wetting current for more sophisticated microphone assemblies, such as those that incorporate digital signal processors (DSPs), which receive power from an auxiliary power source. The present invention allows connectors to be used that have non-precious metal contacts, which reduces the cost of the interface while at the same time providing a reliable connection between the microphone assembly 2500 and the electronic assembly 2502. The possible selection of values for resistors R5, R6, R8, R11, R12 and R13 can widely vary provided that the gain and bandwidth of the microphone assembly and any associated amplifiers are not adversely affected. If desired, one of resistors R5 or R6 can be replaced with a short. Also, resistors R11, R12 and R13 can be replaced with shorts, if desired. The value for resistors R8 and R5 or R6 are then selected to provide an appropriate amount of wetting current. For example, if VAUDIO is twelve volts and a one milliampere (mA) wetting current is desired; if a 2 k/Ω resistor is selected for resistor R5 and resistors R6, R11, R12 and R13 are shorts, then a 10 k/Ω resistor is selected for resistor R8. One of ordinary skill in the art will appreciate that resistors can be more generally an impedance (e.g., R8 can be a choke or active circuit). The component values indicated in FIG. 36 provide generally acceptable performance for the microphone assembly utilized.

FIG. 37 depicts yet another embodiment of the present invention where the wetting current is supplied from the auxiliary power supply (V1). The wetting current (DC) is supplied from power supply V1 through resistors R5 and R12, contacts 4 and 2 of a connector J1, a resistor R8, contacts 1 and 3 of connector J1 and a resistor R11. If desired, resistors R11, R12 and R13 can be replaced with shorts. The value for resistors R5 and R8 are then selected to provide an appropriate amount of wetting current. The embodiment of FIG. 37 is particularly useful, from the view point of the manufacturer of microphone assembly 2600, in that the only component that a manufacturer of electronic assembly 2602 need provide is resistor R8, across contacts 1 and 2 of connector J1.

FIG. 38 depicts yet another embodiment of the present invention wherein the input to the electronic assembly 2702, provided from microphone assembly 2700, is balanced. The wetting current (DC) is supplied from power supply (V1) through a resistor R15, a resistor R16, contacts 4 and 2 of connector J1, a resistor R8, contacts 1 and 3 of connector J1 and a resistor R20. If desired, resistors R16, R17 and R20 can be replaced with shorts. The value for resistors R8 and R15 are then selected to provide an appropriate amount of wetting current. The wetting current (DC) can be supplied from a voltage supply, a resistor, a constant current source, inductor or other power source connected to one of the microphone assembly leads. Providing that the microphone has a DC path for it to complete the wetting current circuit, the source of the current is immaterial.

As shown in FIG. 38, the audio is AC coupled from the microphone assembly output stage to the electronic assembly 2702. The present invention can be extended to multiple connectors that may be included within a microphone assembly or an electronic assembly. According to the present invention, all connectors have a DC current flowing through them to maintain a wetting circuit. Thus, oxidation of the contacts will not disadvantageously affect the circuits utilizing embodiments of the present invention. Additionally, the DC voltage of the microphone input can be used to verify interface continuity for built in test capability.

FIGS. 39A-39D show an alternative embodiment of the present invention in which deflector 1670 includes a cloth deflector portion 3000. Cloth deflector 3000 advantageously deflects airflow from the defroster away from the microphone assembly while allowing sound reflecting off the windshield to penetrate the cloth and reach the microphone assembly. Cloth deflector portion 3000 enables deflector 1670 to be made more compact. By making deflector 1670 more compact, it is less likely to strike the windshield and limit upward movement of the rearview mirror assembly towards the windshield. If the deflector were simply made more compact without using cloth deflector portion 3000, it would be much less effective. While cloth deflector portion 3000 extends upward farther than deflector 1670 would otherwise extend, cloth portion 3000 is deformable and does not limit upward movement of the mirror assembly and preferably contacts the windshield to further prevent airflow from reaching the microphone assembly.

Cloth deflector portion 3000 is preferably made of a polyester material having a weave that is open enough to allow sound to pass through without also allowing significant airflow through the cloth. The cloth is preferably the same material that is used for the windscreens built into the microphone housings. A preferred cloth material has 120 μm mesh holes, a 49 cm mesh count, a thread diameter of 80 μm, and a 35% open area. The cloth deflector portion 3000 may be attached to the rear of deflector 1670 by any suitable means such as an adhesive or the like.

Cloth deflector portion 3000 preferably extends behind the microphone assembly to a height higher than the microphone assembly. By so configuring the cloth deflector portion, the cloth deflector is better able to deflect the airflow from the defroster past the microphone assembly. FIG. 40 is a graph showing the microphone output in dBV versus frequency measured with a vehicle defroster turned on full speed for three different configurations. The first configuration had front and rear microphone transducers-mounted on the top of a mirror housing with no air deflector. Plot A in FIG. 40 represents the direct output of the front microphone transducer while plot B represents the direct output of the rear microphone transducer. Plot C represents the output of a microphone assembly having an air deflector similar to that shown in FIGS. 18-20. Plot D represents the output of a microphone assembly having an air deflector with a cloth deflecting portion similar to that shown in FIGS. 39A-39D. As apparent from a comparison of plots C and D shown in FIG. 40, adding a cloth deflecting portion reduces the noise from the defroster approximately 15 dBV from a deflector without such a cloth portion. As apparent from a comparison of plots A, B, and D, the deflector including a cloth deflecting portion reduces the defroster noise approximately 30 dBV relative to a mirror assembly having no deflector.

When a DSP is utilized to process the microphone assembly output signals, it is desirable to provide the DSP with the outputs from two laterally spaced-apart microphone transducers. One example is a microphone assembly utilizing two laterally offset transducers as shown in FIG. 11 and described above. By providing the DSP with two such output signals rather than adding or subtracting the signals from one another first before providing the resultant signal to the DSP, the DSP may adaptively utilize the information from the separate signals. For example, by laterally spacing microphone transducers and providing the separate output signals to a DSP, the DSP may monitor the noise levels on both microphone transducer output lines and select the output of one transducer over the other when excessive noise is produced on the other transducer. It has been discovered that wind noise produced by the defroster and wind arriving from the vehicle windows or moon roof is often quite gusty such that, if the transducers are spaced adequately far apart, the wind noise may temporarily affect one of the two transducers without affecting the other. As will be discussed further below, it is advantageous to angle the central axes of the two laterally separated transducers so as to provide different directional characteristics for each of the transducers such that the DSP may then utilize this additional directional information to reduce the level of noise. As also described below, different directional characteristics may be achieved by modifying the configuration of the housing ports and windscreen(s).

FIGS. 41A-41D show another embodiment of the present invention. According to this embodiment, two separate microphone assemblies 3502 and 3504 are provided on a flat upper surface portion 2005 of mirror housing 1630 that is circumscribed by deflector 1670. Flat surface portion 2005 is preferably angled slightly downward toward the rear of housing 1630 to provide for additional clearance from the windshield. As best shown in FIG. 41D, microphone assemblies 3502 and 3504 are laterally offset from one another relative to the driver, preferably by at least two inches, and have their respective transducer central axes A and B provided at an angle relative to a normal N of the surface of the mirror. By angling the central axes A and B of the transducers within microphone assemblies 3502 and 3504, the directional characteristics of the microphones are further modified (in addition to their lateral spacing) so as to provide a DSP circuit with yet additional information from which to process voice signals and eliminate noise. By so locating the two microphone assemblies 3502 and 3504, they tend to receive different airflow impulse. By angling the transducers away from one another so that their central axes A and B are not parallel to one another and are angled with respect to normal N, it is more likely that only one of the two microphone assemblies will be severely impacted by a wind gust at the same moment in time. Preferably, wind deflector 1670 is utilized to deflect the laminar airflow coming from the rear of the mirror housing over the microphone assemblies. Any side deviation will deflect the flow from one transducer as it drives toward the second. The end result is one transducer is left free from wind excitation. Since this effect causes great differences with relatively close spacing, the desirable acoustic properties associated with a fairly close spacing are preserved. The end result is all of the benefits from the use of an air deflector are obtained when dealing with airflow arriving from a central defroster vent. This embodiment assures that in the case of a deflection of the airflow, only one transducer is likely to be impacted. The other transducer is, therefore, free from gross airflow noise.

As described below it is possible, and sometimes preferable, to include both transducers for the microphone assemblies 3502 and 3504 within the same windscreen and enclosure. In some circumstances, it may be preferable to use two acoustically separated windscreens. The use of two separate windscreens assures that the transducers will be reacting only to local wind impact. This further assures that native airflow differences will be retained after the application of conventional airflow defense.

As shown in FIGS. 41A-41D, a separator 3500 may be provided between microphone assemblies 3502 and 3504. Separator 3500 provides a physical side airflow deflector. In this manner, the transducer provided on the leeward side of separator 3500 is totally free from airflow impact. Separator 3500 increases the difference between the two transducer(s) reaction to airflow arriving from the side rather than from below.

By rotating the transducers relative to the mirror and/or to each other, airflow difference is further increased. In addition, the resulting change in aiming angle creates the opportunity to achieve a degree of acoustic noise reduction through transducer selection. If airflow is not the dominant noise, a significant difference in acoustic noise resulting from the different null locations can be used by the DSP for noise reduction through the selection of one of the two transducers. For example, when the left transducer has a null shifted right and the right transducer has a null shifted left, and when there is more noise on the left transducer, the DSP software would select the right transducer and, with no additional processing, achieve noise reduction with no impact on the signal quality.

The polar differences between transducers 3502 and 3504 may be exploited with essentially no on-axis difference. During periods where the noise in both signals is of the same relative magnitude, a comparison of the spectrums will reflect the relative polar difference at the angle on entry. From this difference and pattern matching to the location that would yield the difference, the location of the sound can be determined. Once the location difference pattern is established, a spectral band not fitting the pattern can be safely removed from the signal. The fundamental advantage of all of the above actions pertaining to the embodiment shown in FIGS. 41A-41D is that the resulting audio signal is undistorted and has a consistent frequency response. This is in contrast to conventional DSP processing where the process leaves artifacts and is inherently a high distortion process.

Also, by laterally spacing two transducers and providing them on a mirror, the time of arrival can additionally be used to determine the location of a sound burst. Any burst not arriving with the time difference associated with the driver is not passed.

A preferred construction of a microphone assembly is described below with respect to FIGS. 42-49, in which the ports, windscreen, and/or the first and second transducers are configured such that the null of a first polar sensitivity pattern associated with the first transducer is aimed at the driver of the vehicle, and the null of a second polar sensitivity pattern associated with the second transducer is aimed at the front passenger area of the vehicle. In general, the first and second transducers are spaced closely together in a relatively small and narrow microphone housing having a windscreen with very high acoustical resistivity (i.e., about 8 to 9 acoustic ohms/cm₂) disposed across the ports of the housing. This approach seeks to maximize the correlation of noise in the two transducers and de-correlation of the speech signals. DSP processes can then subtract one from the other, greatly reducing the noise and enhancing the signal content. This design is very effective against wind noise and acoustic noise in highly reverberant conditions. It can also differentiate between passenger and driver side noise or speech.

By rotating the polar sensitivity patterns that would otherwise be exhibited by the two transducers such that they have their nulls aimed at either the driver or the front passenger, the forward lobes of the polar patterns partially overlap which improves noise correlation. Close spacing and possibly a common frontal feed structure assure wind excitation will be highly correlated as well. Since noise from the center and front of the vehicle and air flow noise are usually the dominant noises, addressing these effectively is very significant. Aiming the null of one transducer away from the cab may seem to be counter intuitive as it decreases the driver content, but in this construction, one transducer remains almost as sensitive to the driver and the very low driver signal content in the signal from the other transducer assures the driver signal will emerge from the subtraction-like process in the DSP. Very significant is the fact that the noise in both transducers is nearly identical. The null steering described above may be achieved frequency band by frequency band so polar complexity due to the mirror and other factors can be compensated as well. Once accomplished for a condition, no further processing would be needed and no distortion would be caused.

The inventive microphone construction described generally above and in detailed embodiments below, achieve performance levels only previously achieved by systems using transducer arrays that consume significantly larger spaces and require positioning in multiple locations on a mirror with resulting cabling and other secondary cost aspects. The inventive microphone construction is preferably located on the top of a rearview mirror assembly in an area proximate a deflector as discussed above. Nevertheless, the inventive microphone may be mounted at other locations on a mirror assembly, including on the mirror assembly mounting structure, as well as in any other vehicle accessory such as a headliner, sun visor, overhead console, A-pillar, or a console extending between the headliner and a mirror assembly.

Using the above inventive microphone construction, the associated DSP software may process the two transducer signals by adjusting long-term subtraction during non-speech times to the lowest possible value. This may be in the form of sensitivity changes by frequency band such that non-speech times for that band were minimal. This assures that noise is at the lowest U value after subtraction. Also, during driver speech, the output is minimized from the virtual driver microphone created by the inventive microphone construction. During front passenger speech, the output from the virtual passenger microphone is minimized. A starting point from both of these minimizations can be in the form of a calibration using a sound source in an actual vehicle. This can be real time or in the form of stored vehicle specific values. In other words, the DSP software is given coefficients for computing these two special locations either via calibration of the current system or from data obtained from a test system.

An additional advantage of this construction is its inherent noise cancellation. Echo tends to enter both transducers at the same phase and strength so it will cancel like any of the other noises. This is also true of road noise coming thee the rear center of the vehicle.

Four different microphone assembly configurations that achieve these benefits are discussed below.

FIG. 42 shows a first construction of a microphone assembly 3600 employing the above features. As shown, a first transducer 3602 and a second transducer 3604 are mounted with their front surfaces 3606 and 3608, respectively, facing one another. First and second transducers 3602 and 3604 are further aligned with their central axes being co-linear. Both transducers are housed in a common microphone housing 3610, which is shown in outline in FIG. 42 and shown perspectively in FIGS. 43A and 43B. First transducer 3602 generally faces the front passenger and second transducer 3604 generally faces the driver.

Microphone housing 3610 includes numerous ports. Specifically, housing 3610 includes four upper/side ports 3612 a-3612 d resembling elongated slots that extend sideways across the top 3614 and sides 3616 a and 3616 b of housing 3610. Four ports 3618 a-3618 d are provided in the front surface 3620 (i.e., the side of the housing facing the rear of the vehicle) of housing 3610. In the rear surface 3622 of housing 3610 are provided two ports 3624 a and 3624 b, which are spaced apart from one another by a distance exceeding at least one to two times the size of the port openings. Two additional rear ports 3626 a and 3626 b may be provided between ports 3624 a and 3624 b, although, for the reasons stated below, ports 3626 a and 3626 b are preferably plugged or not present or otherwise open.

A windscreen material (not shown) is preferably sealed across each of the open ports of by housing 3610. This windscreen preferably has an acoustic resistivity of between about 8 to 9 acoustic ohms per square centimeter. This greatly reduces wind flow noise, while permitting null steering to aim the nulls at the driver and the front passenger seat.

FIG. 44 shows the two polar sensitivity patterns for the two transducers 3602 and 3604 of the microphone assembly 3600 shown in FIGS. 42, 43A and 43B. As will be apparent from FIG. 44, the nulls of the two patterns are aimed at either the driver (at about 60 degrees) or the front passenger (at about 300 degrees). This is achieved by blocking or eliminating ports 3626 and is aided by using a high resistivity windscreen and a relatively small and narrow acoustic chamber in housing 3610.

A second configuration for achieving similar advantages includes first and second transducers 3602 and 3604 aligned in the same manner shown in FIG. 42. The microphone assembly 3650 according to this embodiment differs, however, in that the microphone housing 3660 includes different ports that are plugged or eliminated. Specifically, in this configuration, which is shown in FIGS. 45A and 45B, front ports 3618 a and 3618 b are plugged or otherwise eliminated, rear port 3626 a is-open, and rear ports 3626 b and 3624 b are plugged or otherwise eliminated. Such porting creates a non-symmetric port configuration that accounts for rotation of the rearview mirror assembly (when the microphone assembly is mounted on the rearview mirror). FIG. 46 shows the two polar patterns associated with the two transducers 3602 and 3604 when used in the housing 3660 shown in FIGS. 45A and 45B. One benefit of plugging or eliminating some of the ports, particularly in the rear of the housing, is that this further blocks the direct air flow on the transducers thereby lowering airflow noise.

FIG. 47 shows a third microphone assembly 3700 that achieves null steering and its inherent benefits. This third construction differs in that the microphone housing 3710 (FIGS. 48A and 48B) does not have any of the aforementioned ports plugged or eliminated. Instead, the nulls of the polar patterns are aimed by rotating second transducer 3604 thirty degrees so that its front surface is aimed more directly at the driver. The transducers should be closely spaced together to avoid phase differences, and should thus preferably be spaced with their diaphragms about one half inch apart.

FIG. 49 shows a fourth microphone assembly 3750 that achieves null steering and its inherent benefits. This fourth construction utilizes the same housing 3710 (shown in FIGS. 48A and 48B) as the third construction, but differs from the third construction in that the first and second transducers 3602 and 3604 are both rotated such that the rear surface of the first transducer 3602 more directly faces the driver and the rear surface of the second transducer 3604 more directly faces the front passenger. The each transducer is preferably rotated about 25 degrees with an included angle between the front surfaces of the transducers at about 50 degrees, however good performance is possible with each transducer rotated anywhere from zero to 60 degrees. The preferred rotation is dependent on the vehicle and the assumed rotation of the mirror (when disposed thereon). The rotation angle is most preferably two times the assumed mirror rotation angle. A typical range of assumed mirror rotation angles is between 10 and 25 degrees thus yielding a typical preferred transducer rotation angle of 20 to 50 degrees. In this construction, the driver speech enters the null angle of one transducer and had very little driver speech content, while the driver speech enters the other transducer at 90 degrees to its null and has content roughly 6 dB below the on-axis, but still far greater than the null of the other. By aiming the frontal lobes of the transducers towards the same point on the windshield, equal amounts of noise are present so that when the two signals from the two transducers are subtracted, the noise cancels.

Another embodiment of the present invention is shown in FIGS. 50A-50E. In general, DSP processes relating to microphone arrays, beam forming, and polar steering exploit predictable phase differences between the signals obtained from transducers located at different locations. This, in turn, requires transducers to be spaced close enough to present phase difference inversion for the highest frequency addressed by the process. The embodiment discussed below uses true time of arrival and as such can use far greater spacing or one large spacing over the entire speech bandwidth. The present embodiment uses the difference in polar response between the two transducers as a location determining mechanism. Unlike second order concepts, use of the difference in polar response is also independent of spacing. This concept can be implemented to separate sub-bands on the basis of origin and relative magnitude. Similar to the embodiment disclosed above with reference to FIGS. 41A-41B, the present embodiment uses the concept of gating. The conditions determine whether a signal or signal component are passed. This is in contrast to techniques that filter by adding or subtracting to form the passed signal. The advantage is that there is less distortion and fewer limitations on the design of the system. In broad terms, this embodiment of the invention extracts wanted sound signals from high levels of ambient noise.

This embodiment effectively creates two electronic ears that will supply signals that are free of non-acoustic noise and rich in data supporting advanced DSP processes. Specifically, these artificial ears are free of airflow and vibration noise. The degree of airflow resistance being such that flow noise is insignificant relative to the threshold of concern. Therefore, the present embodiment has no detrimental effect on resulting DSP operations. The freedom from non-acoustic noise and the presence of very significant and consistent position is then used to define a series of processes capable of extracting very natural sound and spectral content speech from vehicle conditions severe enough that speech quality is typically degraded to the point of poor vocal recognition performance. This embodiment works particularly well when provided on a rearview mirror of a vehicle insofar as the mirror is effectively positioned in “free space” and positioned such that the maximum angular separation exists between sound source locations. The preferred form uses other aspects of the mirror location such as the presence of the windshield to predict noise arrival angles and perfect the artificial ears ability to operate effectively in this environment.

Typically, microphones in automotive applications produce very high outputs as the result of the air flowing past them. In contrast, ears have virtually no airflow sensitivity. Since airflow noise has none of the relationships expected in acoustic noise, it interferes with noise reduction processes. Artificial ears are achieved by laterally separating the microphone assemblies 3802 and 3804 at opposite ends of a mirror housing 1630 (preferably spacing the assemblies at least about 5 cm apart, more preferably about 18 cm) and by hyper-extending the “D” of the transducers 3820 to at least about 3.5 mm, more preferably to at least about 10 mm. This creates a very high acoustic sensitivity of one component of the audio sensing that a microphone utilizes. A secondary rear cavity (3826, FIG. 50E) of greater volume is created with an acoustic resistor 3828 placed at a rear port 3808 with the cavity between resistor 3828 and the rear of a transducer 3820. This cavity 3826 increases the sound sensing mechanism to restore the relationship needed to achieve the desired polar properties. A high acoustic resistance cover 3822 similar to 3828 is placed over external forward port 3806 to severely damp the ports. This very high damping of both ports lowers the acoustic sensitivity and the airflow noise. Since the dominant vibration to microphone output conversion comes from the vibration of the microphone against static air, vibration noise is also reduced.

The end result is a normal acoustic sensitivity with profoundly lower airflow and vibration noise. Since this is a fundamental improvement in signal to airflow noise, it applies to all airflow coming from any direction. The resulting long “D” of the microphone assembly is positioned along the rear surface of the mirror housing along a diagonal with the lower portion angled inward toward the middle and the upper portion angled outward. This results in a high degree of noise rejection for sounds coming from below the mirror along the windshield boundary and a great deal of difference for sounds coming at an angle to the common axis between the two due to the angular positioning.

The use of the hyper-long “D” improves greatly the directional properties for the majority of the passed band. Higher frequencies are not necessarily helped. This deficit is addressed by adding directional means such as a partially horned (or flared) opening 3810, 3816 toward the forward port 3806, 3812. While frequency response may be negatively impacted, this aspect maybe corrected by electronic equalization ideally done prior to digitization.

By providing similar constructions on opposite sides of the rearview mirror housing 1630, two signals may be obtained that are free from airflow noise and that reject the dominant spatial noise location, each with a very high degree of directionality and each aimed to provide a great degree of spectral difference related to source angular position. Since microphone assemblies 3802 and 3804 are widely spaced, there is also a significant arrival time difference. These “artificial ears” produce all the data types and freedom from unwanted airflow and mechanical noise needed for the companion DSP algorithms. The DSP algorithms may thus exploit the additional data and enjoy the freedom from non-acoustic noise content.

The preferred default for most applications is to have the DSP provide no signal until speech is detected. Thus, the preferred process is based on not passing a signal unless the speech detection criteria are met as opposed to always passing the signal and trying to lower the noise content. While this may provide processing delays, compensation can be accomplished by providing a slight delay in the delivered signal to allow processing and yet not use the first utterance of a spoken word. The process begins with the determination in each ear channel that a change in the input has occurred consistent with a speech utterance. This is a well-established DSP process.

The difference in the case of the present invention is that this action is done in two channels by only passing speech-like events. The present invention avoids times when speech content is so low that it is virtually useless. The threshold may be set higher for more robust vocal recognition and better speech quality or may be set lower for higher noise to speech situations. The time of arrival may then be utilized to begin the process of processing only that speech from the desired spatial location (i.e., the location in which the driver or other passengers are located). Incorrect arrival time difference will narrow the possibly conflicting noises to those arriving from a line of source locations around the central axes of the two ports 3806 and 3812. Then, by applying the DSP's stored knowledge of the desired user, and of human speech in general, the user's fundamental frequencies may be determined to create a comb-pass filter. The result is that only those bands likely to contain speech are present. This is most effective in the bands dominated by vocal cord sounds.

At this point, any bands are passed that are likely to contain speech and only those sounds from the correct location and only those sounds that vary like speech are passed. The relative spectral content may then be used to further add location separation. For every spatial location, one can map the relative frequency responses for that entry angle for both signals. One would only need to address those regions where speech bands are present. By comparing the difference in spectral content of the two signals from microphone assemblies 3802 and 3804, the DSP can determine if the current dominant signals are coming from the focused location. Even more useful, the DSP can determine if a time varying band in the passed bands originates from other than the focused location. This is achieved by comparing the relative magnitudes to the response maps. For example, if the difference should be +3 dB left versus right, and the difference is −2 dB, the DSP will know that this particular band did not originate at the focused spatial location and can be removed. At this point, only speech sounds from the desired location have been passed.

At this time, the DSP's knowledge of the target user may be used to reconstruct missing speech bands. Specifically, there will be bands where there is important speech content, but the speech content is not large enough to be significant and will be lost in the filtering process. Humans know what a speaking person sounds like from less noisy times and apply that knowledge during very high noise conditions to extrapolate the speech bands. The DSP may use the same form of processing. Specifically, over time, the DSP may generate a harmonic amplitude map for the range of observed fundamental frequencies. If the fundamental frequency is known, it may be used as the map reference and extract the relative magnitudes of the harmonics. Since every human has a consistent harmonic map, as the result of fixed head cavities, the DSP can apply the known harmonic amplitudes to estimate the missing ones. For example, human speech usually loses its high frequency content in very high noise environments. In lesser noise, where some of the high bands are not lost, knowledge may be gained of this speech and used to fill in the missing bands in the higher noise environments.

The sequence of filters and the number of filters used can vary depending on need, benefit, or cost. The key being to exploit the rich data derived from the artificial ears and the knowledge of the speaking human to yield speech free from the detrimental effects of high noise. With reference to FIGS. 50A-50E, it is noted that the two microphone assemblies 3802 and 3804 are integrated into the rear of the mirror housing 1630 and are disposed such that the central axes of the transducers provided in these assemblies are at an angle with respect to one another and with respect to a normal to the mirror surface. Further, the transducer central axes are aimed at an angle upward relative to the position of the driver. This allows the microphone assemblies to be integrated more to the rear of the mirror assembly and somewhat obscured from the view of the driver or other passengers.

While the above embodiment addresses the problems in the automotive environment on a broadband basis, the transducers used may be omni-directional and the DSP could utilize time of arrival for the lower frequency bands while using the directional characteristics provided by the horn at the forward port for the higher frequency bands.

When a microphone assembly 3900 is remotely located in the vehicle from an associated DSP circuit 3912 (FIG. 51), induced noise is typically present on the electrical conductor 3908 extending from the microphone assembly to the DSP circuit. To eliminate this noise, a reference line 3901 is also run from the location of the microphone assembly to the DSP circuit. An impedance matching circuit 3903 is provided at the microphone end of the reference line 3901 to match the impedance of the microphone transducer 3902. Because only induced noise is present on this reference line, the induced noise may be detected and then subtracted from the signal delivered from the microphone assembly. When more than one signal from one or more microphone assemblies are to be delivered to a DSP circuit, the number of lines that must be run through the vehicle are correspondingly multiplied. For example, for a system utilizing two microphone transducers with two corresponding output signals to be delivered to the DSP circuit, at least one, if not two, reference lines may be required. The addition of all these electrical conductors extending through the vehicle adds significantly to the cost of such a system. Accordingly, the need exists for a system that would allow for more than one transducer to be utilized while minimizing the number of electrical conductor lines that need to be run to a remote DSP circuit.

To eliminate the need for the reference lines in the above system, a circuit such as that shown in FIG. 52 may be utilized. Specifically, with two transducers 3902 and 3904 provided in a mirror assembly 3906, the respective output lines 3908 and 3910 are provided to a DSP circuit 3912 that is remotely located from the rearview mirror assembly or other vehicle accessory in which the microphone transducers are mounted. A phase inverter 3914 is provided in the path of one of lines 3908 and 3910 in order to invert the phase of the acoustic signal sensed by one of the two transducers. DSP circuit 3912 will know in advance that the audio signal from this particular transducer is inverted and process it accordingly. The noise that is induced on the two lines, however, between the mirror assembly and the DSP circuit will not be inverted. Thus, the DSP circuit may differentiate the audio signals from the noise that is common on both lines 3908 and 3910. Since there is little time of arrival or phase difference between the two fairly closely spaced microphone transducers, there will be very little, if any, driver speech content lost by the cancellation process. The only acoustic content that might be lost is noise or other sound arriving such that significant phase differences in the outputs occur. The DSP may alternatively re-invert the phase of the second signal and then differentiate the audio signals from the line-induced noise based on common signals that are out of phase with one another.

The microphone assembly described above can be incorporated anywhere in the interior of a vehicle. For example, the microphone assemblies can be located within the interior trim of a vehicle, an overhead console, a visor, a rearview mirror assembly, the housing of an electronic rear vision display, or within a mini-overhead console provided near the rearview mirror mounting structure on the windshield. In a preferred embodiment, the microphone assembly is incorporated within or on an automotive rearview mirror assembly. If desired, the contacts of the connector that couples the microphone assembly to the electronic assembly can be plated with a precious metal (e.g., gold or silver) to facilitate improved continuity.

Thus, it can be seen that an improved microphone assembly for vehicles is disclosed. It is envisioned that the microphone assembly may be applied to a wide variety of performance applications, in that the microphone assembly can include a single transducer or multiple transducers. By using multiple transducers, significantly improved performance is achieved. Use of one transducer, having a single diaphragm or multiple diaphragms suitably ported to achieve a desired directional pattern, offers a lower cost microphone that can be used in the same mount and housing as the multiple transducer microphone assembly, in applications where the higher performance is not required.

The rearview mirror assembly 4001 according to an alternative embodiment is shown in FIGS. 53A-53E. The mirror assembly 4001 includes a mirror 4008 mounted in an elongated mirror housing 4006 pivotably carried on mirror support 4004. The mirror 4008 may be any conventional interior rearview mirror, such as a prismatic mirror of the type used with a mirror housing manually adjustable for daytime and nighttime operation, or a multiple element mirror effecting automatic reflectivity adjustment, such as an electrooptic or electrochromic mirror. The elongated mirror housing 106 may be of any conventional manufacture such as integrally molded plastic.

As will be explained in more detail below, two microphone assemblies 4020 a and 4020 b are provided along the back surface 4007 of mirror housing 4006 (i.e., that surface facing forward of the vehicle). As apparent from FIG. 53A, microphone assembles 4020 a and 4020 b are not visible from the front of the mirror assembly and hence are generally not visible to the vehicle occupants.

In general, DSP processes relating to microphone arrays, beam forming, and polar steering exploit predictable phase differences between the signals obtained from transducers located at different locations. This, in turn, requires transducers to be spaced close enough to present phase difference inversion for the highest frequency addressed by the process. The first embodiment discussed below uses true time of arrival and as such can use far greater spacing or one large spacing over the entire speech bandwidth. The present invention uses the difference in polar response between the two transducers as a location determining mechanism. Unlike second order concepts, use of the difference in polar response is also independent of spacing. This concept can be implemented to separate sub-bands on the basis of origin and relative magnitude. The present embodiment uses the concept of gating. The conditions determine whether a signal or signal component are passed. This is in contrast to techniques that filter by adding or subtracting to form the passed signal. The advantage is that there is less distortion and fewer limitations on the design of the system. In broad terms, this embodiment of the invention extracts wanted sound signals from high levels of ambient noise.

This alternative embodiment effectively creates two electronic ears that will supply signals that are free of non-acoustic noise and rich in data supporting advanced DSP processes. Specifically, these artificial ears are free of airflow and vibration noise. The degree of airflow resistance being such that flow noise is insignificant relative to the threshold of concern. Therefore, the present embodiment has no detrimental effect on resulting DSP operations. The freedom from non-acoustic noise and the presence of very significant and consistent position is then used to define a series of processes capable of extracting very natural sound and spectral content speech from vehicle conditions severe enough that speech quality is typically degraded to the point of poor vocal recognition performance. This embodiment works particularly well when provided on a rearview mirror of a vehicle insofar as the mirror is effectively positioned in “free space” and positioned such that the maximum angular separation exists between sound source locations. The preferred form uses other aspects of the mirror location such as the presence of the windshield to predict noise arrival angles and perfect the artificial ears' ability to operate effectively in this environment.

Typically, microphones in automotive applications produce very high outputs as the result of the air flowing past them. In contrast, ears have virtually no airflow sensitivity. Since airflow noise has none of the relationships expected in acoustic noise, it interferes with noise reduction processes. Artificial ears are achieved by laterally separating the microphone assemblies 4020 a and 4020 b at opposite ends of mirror housing 4006 (preferably spacing the assemblies at least about 5 cm apart, more preferably about 18 cm) and by hyper-extending the “D” of the transducers 4025 a and 4025 b of respective assemblies 4020 a and 4020 b to at least about 8 mm, more preferably to at least about 15 mm. This creates a very high acoustic sensitivity of one component of the audio sensing that a microphone utilizes. A secondary rear cavity (4026, FIG. 53E) of greater volume is created with an acoustic resistor 4028 a placed at a rear port 4024 a with the cavity between resistor 4028 a and the rear of a transducer 4025 a. This cavity 4026 a increases the sound sensing mechanism to restore the relationship needed to achieve the desired polar properties.

A high acoustic resistance cover 4030 a similar to 4028 a is placed over external forward port 4022 a to severely damp the ports. This very high damping of both ports lowers the acoustic sensitivity and the airflow noise. Since the dominant vibration to microphone output conversion comes from the vibration of the microphone against static air, vibration noise is also reduced. The end result is a normal acoustic sensitivity with profoundly lower airflow and vibration noise. Since this is a fundamental improvement in signal to airflow noise, it applies to all airflow coming from any direction. The resulting long “D” of the microphone assembly is positioned along the rear surface of the mirror housing along a diagonal with the lower portion angled inward toward the middle and the upper portion angled outward. This results in a high degree of noise rejection for sounds coming from below the mirror along the windshield boundary and a great deal of difference for sounds coming at an angle to the common axis between the two due to the angular positioning.

The use of the hyper-long “D” improves greatly the directional properties for the majority of the passed band. Higher frequencies are not necessarily helped. This deficit is addressed by adding directional means such as a partially horned (or flared) opening 4032 a, 4032 b toward the forward port 4022 a, 4022 b (FIG. 53B-53D). While frequency response may be negatively impacted, this aspect may be corrected by electronic equalization ideally done prior to digitization.

By providing similar constructions on opposite sides of the rearview mirror housing 4006, two signals may be obtained that are free from airflow noise and that reject the dominant spatial noise location, each with a very high degree of directionality and each aimed to provide a great degree of spectral difference related to source angular position. Since microphone assemblies 4020 a and 4020 b are widely spaced, there is also a significant arrival time difference. These “artificial ears” produce all the data types and freedom from unwanted airflow and mechanical noise needed for the companion DSP algorithms. The DSP algorithms may thus exploit the additional data and enjoy the freedom from non-acoustic noise content.

The preferred default for most applications is to have the DSP provide no signal until speech is detected. Thus, the preferred process is based on not passing a signal unless the speech detection criteria are met as opposed to always passing the signal and trying to lower the noise content. While this may provide processing delays, compensation can be accomplished by providing a slight delay in the delivered signal to allow processing and yet not use the first utterance of a spoken word. The process begins with the determination in each ear channel that a change in the input has occurred consistent with a speech utterance. This is a well-established DSP process. The difference in the case of the present invention is that this action is done in two channels by only passing speech-like events. The present invention avoids times when speech content is so low that it is virtually useless. The threshold may be set higher for more robust vocal recognition and better speech quality or may be set lower for higher noise to speech situations. The time of arrival may then be utilized to begin the process of processing only that speech from the desired spatial location (i.e., the location in which the driver or other passengers are located). Incorrect arrival time difference will narrow the possibly conflicting noises to those arriving source locations around the line connecting the two transducer's center lines. Then, by applying the DSP's stored knowledge of the desired user, and of human speech in general, the user's fundamental frequencies may be determined to create a comb pass filter. The result is that only those bands likely to contain speech are present. This is most effective in the bands dominated by vocal cord sounds.

At this point, any bands are passed that are likely to contain speech and only those sounds from the correct location and only those sounds that vary like speech are passed. The relative spectral content may then be used to further add location separation. For every spatial location, one can map the relative frequency responses for that entry angle for both signals. One would only need to address those regions where speech bands are present. By comparing the difference in spectral content of the two signals from microphone assemblies 4020 a and 4020 b, the DSP can determine if the current dominant signals are coming from the focused location. Even more useful, the DSP can determine if a time varying band in the passed bands originates from other than the focused location. This is achieved by comparing the relative magnitudes to the response maps. For example, if the difference should be +3 dB left versus right, and the difference is −2 dB, the DSP will know that this particular band did not originate at the focused spatial location and can be removed. At this point, only speech sounds from the desired location have been passed. At this time, the DSP's knowledge of the target user may be used to reconstruct missing speech bands. Specifically, there will be bands where there is important speech content, but the speech content is not large enough to be significant and will be lost in the filtering process. Humans know what a speaking person sounds like from less noisy times and apply that knowledge during very high noise conditions to extrapolate the speech bands. The DSP may use the same form of processing. Specifically, over time, the DSP may generate a harmonic amplitude map for the range of observed fundamental frequencies. If the fundamental frequency is known, it may be used as the map reference and extract the relative magnitudes of the harmonics. Since every human has a consistent harmonic map, as the result of fixed head cavities, the DSP can apply the known harmonic amplitudes to estimate the missing ones. For example, human speech usually loses its high frequency content in very high noise environments. In lesser noise, where some of the high bands are not lost, knowledge may be gained of this speech and used to fill in the missing bands in the higher noise environments.

The sequence of filters and the number of filters used can vary depending on need, benefit, or cost. The key being to exploit the rich data derived from the artificial ears and the knowledge of the speaking human to yield speech free from the detrimental effects of high noise. With reference to FIGS. 53A-53E, it is noted that the two microphone assemblies 4020 a and 4020 b are integrated into the rear of the mirror housing 4006 and are disposed such that the central axes of the transducers provided in these assemblies are at an angle with respect to one another and with respect to a normal to the mirror surface. Further, the transducer central axes are aimed at an angle upward relative to the position of the driver. This allows the microphone assemblies to be integrated more to the rear of the mirror assembly and somewhat obscured from the view of the driver or other passengers.

While the above embodiment addresses the problems in the automotive environment on a broadband basis, the transducers used may be omni-directional and the DSP could utilize time of arrival for the lower frequency bands while using the directional characteristics provided by the horn at the forward port for the higher frequency bands.

A preferred second embodiment of an interior rearview mirror assembly 4101 of the present invention is shown in FIGS. 54A-54D. The front view of interior rearview mirror assembly 4101 is not shown insofar as its appearance would be similar to the interior rearview mirror assembly 4001 shown in FIG. 53A. As shown in FIGS. 54A-54D and as described below, the microphone assemblies 4120 a and 4120 b are also mounted on the back surface 4107 of the mirror housing 4106 and are not visible from the front of the mirror assembly.

The microphone assemblies 4120 a and 4120 b are preferably mounted on the mirror assembly and may be substantially identical. Only one of the two microphone assemblies is shown and described in detail. Microphone assembly 4120 a includes a microphone housing 4115, a transducer 4125, and a circuit board 4126. The microphone housing 4115 (FIGS. 55-57) is generally rectangular, although the housing could have a generally square foot print, an elongated elliptical or rectangular foot print, or any other shape desired by the microphone designer. The microphone housing 4115 includes front ports 4116 that face upwards and rear ports 4118 that downward. The ports 4116 and 4118 provide sound passages through the microphone housing. The ports 4116, 4118 can have any suitable opening shape or size. In the embodiment shown in FIGS. 54A-62, microphone housing 4115 includes four front ports 4116 a-4116 d provided in the front surface (i.e., the side of the housing facing upward) of microphone housing 4115, and four rear ports 4118 a-4118 d in the rear surface (i.e., the side of the housing facing downward) of microphone housing 4115. The front and rear ports are similar in shape and position and are preferably symmetrical.

The microphone housing 4115 also includes resilient mounting tabs 4140 for insertion into openings (not shown) in the back surface of mirror housing 4106 to thereby secure microphone assembly 4120 a to mirror housing 4106. For example, the tabs can be generally L-shaped in profile for insertion into the mirror housing 4106. Alternately, the tabs 4140 can be elongate snap connectors that slide into an opening (not shown) in the back surface of the mirror housing and snap into engagement with the inside surface of the mirror housing 4106 after full insertion. The microphone housing 4115 can be integrally molded plastic, stamped metal, or of any other suitable manufacture.

The transducers 4125 used in the microphone assemblies 4120 a and 4120 b are preferably substantially identical. The transducers 4125 can be any suitable, conventional transducers, such as electret, piezoelectric, or condenser transducers. The transducers may be, for example, electret transducers such as those commercially available from Matsushita of America (doing business as Panasonic), and may advantageously be unidirectional transducers. If electret transducers are employed, the transducers can be suitably conditioned to better maintain transducer performance over the life of the microphone assemblies. For example, the diaphragms of the transducers 4125 can be baked prior to assembly into the transducers.

The circuit board 4126 has a conductive layer on one of its surfaces that is etched and electrically connected to the leads of transducer 4125. The transducer leads may be connected to a pre-processing circuit that may be mounted to the conductive layer of circuit board 4126. Although the pre-preprocessing circuit can be mounted on the circuit board 4126 in the microphone housing, it will be recognized that the such a circuit as well as other circuits such as a digital signal processor (DSP) can alternatively be mounted on a printed circuit board 4127 (FIG. 54D) in the mirror housing 4106, and further that in the case of an electrooptic mirror, such as an electrochromic mirror 4108, the circuits can be mounted on a common circuit board with the mirror electrical components, or the circuits and the mirror electrical components can be mounted on separate circuit boards within the mirror housing 4106. Further still, such processing circuits may be located elsewhere in the vehicle, such as in the mirror assembly mount, an overhead console, an on-window console, an A-pillar, or in other locations. Examples of such processing and pre-processing circuits are disclosed in commonly assigned U.S. Pat. No. 6,882,734.

The electrical connection of the transducer leads and the components of an pre-processing or other processing circuit, are preferably by electrical traces in the conductive layer of the circuit board, formed by conventional means such as etching, and vias extending through the dielectric substrate of the printed circuit board. The circuit board may include holes for receipt of posts on microphone housing 4115. Such posts may be heat-staked to the circuit board substrate after the posts are inserted through the holes therein to secure the connection of the circuit board 4126 to the microphone housing 4115 and insure that the microphone assembly provides acoustically isolated sound channels between the transducer 4125 and the ports 4116 and 4118, as described in greater detail herein below.

To assemble the microphone assembly 4120 a, the transducer 4125 is first mounted on the circuit board 4126. As will be described in detail below, an acoustic dam 4130 (FIGS. 58-62) is preferably inserted between the circuit board 4126 and microphone housing 4115. The transducer 4125, circuit board 4126, is then secured to the microphone housing 4115 with the acoustic dam 4130 therebetween.

Microphone transducer 4125 is preferably mounted sideways through a hole 4134 formed in printed circuit board 4126. A portion of transducer 4125 would thus extend below the bottom surface of circuit board 4126 and a portion would also extend above a top surface of printed circuit board 4126. Mounting the transducer in this orientation and position relative to the circuit board provides several advantages. First, the electrical contacts on the transducers may be directly soldered to traces on the printed circuit board. This avoids the need for manually connecting wires to the transducer contacts and subsequently manually connecting those wires to the circuit board. Thus, the transducer may be mounted to the circuit board using conventional circuit board populating devices.

Another advantage of mounting the transducers such that they extend above and below the surfaces of the printed circuit board is that one side of the circuit board may include a conductive layer serving as a ground plane. Such a ground plane may shield the transducers from electromagnetic interference (EMI) that may be produced by other components within the rearview mirror assembly or in other components within the vehicle. Such EMI can introduce significant noise into the signal delivered by the transducers. In a preferred embodiment, each transducer is mounted in a circuit board having a conductive ground plane facing the acoustically active portion of the transducer while the circuit components are mounted to the opposite side.

Microphone subassembly 4020 further includes a windscreen 4042, which protects the transducer and circuit board from the external environment. Windscreen 4042 is preferably made of a hydrophobic heat-sensitive adhesive-coated fabric and is adhesively attached to the underside and inner surfaces microphone housing 4115 across ports 4116 and 4118. Microphone housing 4115 is preferably tightly bonded about circuit board 4126 to provide a water-impervious enclosure for transducer 4125.

While it has been typical in conventional microphones to minimize the acoustic resistivity of a windscreen by increasing the porosity of the windscreen, the microphone assembly of the present invention advantageously utilizes a windscreen with a higher acoustic resistivity by decreasing the porosity of windscreen and yet obtaining not only better water-resistant properties, but to also improved the acoustic characteristics for the microphone assembly. The use of a high resistively windscreen is particularly advantageous when the microphone assembly is mounted on a rearview mirror assembly since significant noise may be introduced from the windshield defroster. Specifically, the acoustic resistivity of windscreen 4142 may be increased to at least about 1 acoustic Ω/cm₂ and preferably has an acoustic resistivity of at least about 2 acoustic Ω/cm₂, and more preferably has an acoustic resistivity of at least about 8 to 9 acoustic Ω/cm₂. Further, as described below, the acoustic resistivity of windscreen 4142 may be varied to also vary the directionality and polarity of the microphone assembly.

With the microphone transducers 4125 of the two microphone assemblies 4120 a and 4120 b sealed in separate housings and having their own windscreens, the ports and acoustic resistivity of the windscreens may be different for the different microphone assemblies transducers so as to compensate for any effects experienced by the transducers as a result of the positioning of the transducers on the vehicle accessory. For example, when one microphone assembly (i.e., 4120 a) is to be positioned closer to the windshield as a result of typical tilting of mirror housing 4106, its polar pattern may be slightly different from that of the other microphone assembly 4120 b. Thus, by selecting an appropriate microphone housing design/port configuration, and windscreen resistivity, the effects of the differences resulting from the positioning of the transducers of the two assemblies may be compensated such that the transducers exhibit substantially similar polar patterns and other characteristics. While the windscreen has been described above as consisting of a hydrophobic fabric, it will be appreciated that the windscreen may be molded integrally across the ports of the microphone housing. Such an arrangement would simplify the manufacturing of the microphone assembly by requiring less parts and less manufacturing steps. Further, it would more likely provide a more effective seal between the windscreen and the microphone housing. To attempt to obtain a required sensitivity accuracy for the transducers, a laser trim tab may be added to the gain stage connected to each transducer. The transducers may then be acoustically excited by a calibrated sound source and the output of the transducers is monitored. The laser trim tab is then trimmed to precisely set the gain and thereby obtain precise sensitivity accuracy.

A problem with mounting microphone subassemblies to the top or back of the mirror housing results from the fact that the microphone assemblies are closer to the windshield. When the windshield defroster is activated, a sheet of air travels upward along the windshield. Thus, when the microphone subassemblies are placed on the back or top of the mirror housing, it is exposed to more airflow as the air from the defroster passes between the mirror housing and the window past the microphone subassembly. This airflow creates turbulence as it passes over the microphone subassembly, which creates a significant amount of noise.

To solve this problem when the microphone assembly is mounted to the top of a rearview mirror housing, commonly-assigned U.S. Pat. No. 6,882,734 and PCT Application Publication No. WO 01/37519 A2 disclose the use of a deflector that extends upward from the rear of the mirror housing so as to smoothly deflect the airflow from the defroster over and/or beside microphone subassembly so that it does not impact the transducers or create any turbulence as it passes over and around the microphone assembly. Because the airflow primarily would enter the rear of the microphone subassembly, the deflectors are designed to redirect the air with minimal impact on the frequency response of the microphone subassembly. This is important for high intelligibility in the motor vehicle environment. With no direct air impact and the avoidance of turbulence near the microphone subassembly, the microphone assembly may advantageously be mounted on the top of the mirror housing can offer superior resistance to airflow-generated noise.

As described above, the microphone assemblies used in the second embodiment have rear ports 4118 that open downward. Normally this would pose a serious problem since the defroster airflow would directly strike these rear ports and thus generate significant noise. As described above and in detail below, the use of a very high acoustic resistivity windscreen 4142 significantly reduces the noise level caused by such airflow. Nevertheless, it is also advantageous to configure the back surface 4107 of mirror housing 4106 such that integral deflectors 4146 a and 4146 b are provided proximate the lower (rear) surface of the microphone assemblies 4120 a and 4120 b so as to reduce or prevent such airflow from directly striking the microphone assemblies. Deflectors 4146 a and 4146 b may be provided by mounting the microphone assemblies 4120 a and 4120 b in recessed portions 4148 a and 4148 b of back surface 4107 of mirror housing 4106. Such recesses would each include a wall 4150 a and 4150 b that has a height that is generally equal to or greater than the height of microphone housing 4115. Wall 4150 a and 4150 b may be flat, tapered and/or contoured around the lower wall and one end of microphone housing 4115. Preferably, recesses 4148 a and 4148 b would not have any walls opposite walls 4150 a and 4150 b such that front ports 4116 of microphone housing 4115 open upwards and are unobstructed by any other structure on the mirror housing.

As shown in the drawings, the combination of the mounting of the microphone assemblies 4120 a and 4120 b on the back surface 4107 of mirror housing 4106 and the mounting of the transducers 4125 in microphone housings 4115 in the orientation shown, results in the central axis of the transducers 4125 extending generally vertically. Normal tilting of the mirror housing 4106 may result in the central axis tilted nearly parallel to the windshield 105 of the vehicle 100. As described below, such positioning and orientation of the transducers 4125 results in several advantages.

One advantage is that the transducers may be mounted in a through-hole fashion as discussed above, while the circuit board 4126 may be mounted substantially parallel to a surface of mirror 4108, most likely the rear surface of mirror 4108. If the mirror 4108 is an electro-optic mirror, a mother board 4127 is typically provided in the mirror housing 4106 parallel to the rear surface of mirror 4108 (see FIG. 54D). Thus, circuit board 4126 would be substantially parallel to mother board 4127 and could be readily electrically coupled to mother board 4127 using conventional connector plugs 4128. Additionally, by having both circuit boards in parallel with one another and in parallel with the rear surface of mirror 4108, less space need be provided in mirror housing 4106 to accommodate these components.

By being located on the back 4107 of the mirror housing 4106 and in the basic plane of mirror 4108, the virtual axis of microphone assembly 4120 a is aimed upward. This in turn means the rear aligns with the windshield boundary, since noise is greatest along this boundary this alignment offers the greatest average noise rejection. In other words this aiming condition lowers the noise from common sources including defroster fan and duct noise, road noise, rain noise, and wind-on-windshield noise.

Another benefit of upward aiming and being just behind the forward surface of mirror housing 4115 is freedom from the comb effect. All high frequency sounds from the vehicle cabin enter the microphone by reflecting off the windshield and/or headliner at which microphone assemblies 4120 a and 4120 b are aimed (See FIG. 54C). Direct high frequency sound is stopped by the front surface of the mirror. Since comb effect occurs when two identical signals mix with different arrival times, the removal of the direct sound lowers the high frequency signals to only one. Comb effect is a very disruptive condition as it removes almost completely regions of the band. These missing regions contain important sonic data that when lost impairs voice recognition and it makes human speech sound hollow and reverberant.

Another benefit of mounting the microphone assemblies 4120 a and 4120 b to the rear surface and the ends of mirror housing 4106 is that the mirror physically blocks high frequency sounds coming from directions in which the sound path would pass through the mirror 4108 to reach the microphone assembly 4120 a, 4120 b. Placing the microphone assemblies 4120 a, 4120 b into notched recesses 4148 a, 4148 b at each end the mirror housing 4106 imparts a great deal of increased directional ability in the higher frequency portion of the band roughly 2500 Hz and above.

Prior art array microphones are based on the use of the same basic directional aspect. This is often a requirement such that when time of arrival is adjusted the speech signals will add. Differences in aiming angle would interfere with this addition for sounds coming off axis which the array aiming ability requires. In prior art arrays, the microphone transducers must be placed close enough together to achieve time alignment by simple maximization of signal. This prevents wide spacing relative to the wavelength of the highest frequency sound in the pass band. Conversely, a wide enough separation is often required to have a difference of meaningful size when the wavelength decreases. The combination of these two effects forces the use of more the two transducers to get effective array microphone operation trough the entire audio band.

The inventive second embodiment manifests directional attributes that are nearly identical through the mid and lower frequencies. Since the microphone assemblies are also widely separated they function effectively in the mid and lower frequencies. Since the microphone assemblies are too widely separated for conventional array functionality in the higher frequencies, it may be desirable to add an additional means to achieve beam steering.

The mirror-added directional ability provides this second beam forming means. Since there is very significant difference in the high frequency output for a given point in space, amplitude comparison can be used to augment time of arrival extending beam forming beyond that supported by the spacing. In effect, the two microphone transducers yield the functionality of four.

In terms of spacing dimensions, advantages arise as the spacing is increased from 3 inches, the greatest spacing possible for a top frequency of roughly 5 kHz, with increasing advantage until the spacing increases beyond the point of high frequency directional onset, 2.5 kHz or 6 inches. The onset of high frequency directional function is progressive so the actual range of maximum separation can vary from 5 to 7 inches.

Another advantageous aspect is the styling freedom offered by recessed rear mounting. The microphone is not visible from the cab and lies on a large surface supporting a large microphone with no additional size or protrusions. Further by avoiding the central area of the mirror housing, the microphone assemblies do not interfere with mounting or wiring. Since the center of the mirror housing must be strong to resist vibration avoidance of the center also preserves the ability to effectively use reinforcing ribs and other strength enhancing details.

To gain the full benefits from mounting the microphone assemblies on the rear surface of the mirror housing, acoustic dam 4130 may be employed. This is because the microphone assemblies are preferably recessed into the mirror housing to protect the rear ports 4118 from direct air impingement from defroster airflow. This situation in turn decreases the effective “D” by adding delay to the sound arriving at the rear port. Sound traveling from the rear to the front takes some additional time to reach the rear port. The difference between the arrival at the front or rear forms the phase difference that produces the null. This difference is reduced altering the resulting null angle. In other words, the microphone should be made more directional to have the correct manifested directional properties when recessed into the rear of the mirror housing.

All prior art assumes the transducer portion is free within the containment shell. In other words, sound waves are passing by the transducer and it responds to them as passing waves. In the case of “D” extension a greater portion of the available pressure difference from these passing waves is yielded. This is used to compensate for reduced wave intensity due to the impact of the port resistance of the outer shell.

The acoustic dam 4130 does not function like a “D” extender but rather forms additional pressure difference effectively funneling acoustic energy into the transducer. This is accomplished by dividing the interior space into acoustic zones. It is the difference in external “D” between these regions that causes the increased pressure difference.

For example, in the second embodiment, dam 4130 forms defined regions of the outer grill that impact specific zones since transducer 4125 passes through a hole in dam 4130, one side is the virtual front of the transducer and the other the back. The center of the port area feeding each zone acts like the port of a microphone of that size. In other words, if these ports on the average are 1 inch apart then the microphone has an effective external “D” of 1 inch. The virtual aiming direction is also determined by this center of area location. In other words, if the microphone is aligned straight forward but the two virtual ports are rotated 45 degrees, then the aiming point for the actual microphone will be rotated 45 degrees.

In the second embodiment shown in FIGS. 58-62, dam 4130 does not completely separate the zones it forms when dividing the acoustic chamber defined by the housing 4115 and circuit board 4126. This allows the pressure to equalize between the zones. Flowing air creates different pressures in each zone by connecting these zones this pressure difference is reduced. This connection does not impact acoustic pressure differences because they are the result of a consistent external pressure difference and because flowing air noise is a near DC phenomena. The length of the dam 4130 in relation to the length of the open acoustic chamber area determines the weighting factor of the external ports 4116 and 4118. Those ports near or over the open regions 4132 have little impact on the virtual “D” and conversely those farthest from the openings 4132 have the greatest impact. As a result dam width can be used to tune the design to optimize the desired directional aspects and the flowing air rejection. The best ratios are from 50% dam to 90% dam.

The dam extends and acoustically seals the typically narrow thickness dimension of the microphone housing 4115. Any gap close to the center of the dammed zones allows the pressure difference to cross equalize thereby lowering the difference the transducer perceives. Thus, as shown in FIGS. 58-60 and 62, groove forming members 4150 may be provided on the top of circuit board 4126 so as to receive and hold acoustic dam 4130 and thereby ensure an acoustic seal between the dam and the circuit board. Similarly, a groove 4152 may be provided on the top inner surface of microphone housing 4115 to receive, hold and create an acoustic seal with dam 4130. To enhance the acoustic seal of dam 4130 about the periphery of transducer 4125, an epoxy 4154 may be applied therebetween.

To demonstrate the effectiveness of acoustic dam 4130 in combination with a very high acoustic resistivity windscreen 4142, a three different prototype rearview mirror assemblies were constructed having microphone assemblies similar to the second embodiment described above and shown in FIGS. 54A-62. The first prototype used a windscreen with a low acoustic resistivity fabric. A polar plot was obtained for this first prototype at 1000 Hz. A copy of the polar plot is shown in FIG. 63. Note the directional sensitivity of this polar pattern is generally what is desired so as to have greatest sensitivity upward (i.e., at 0 degrees) and the lowest sensitivity downward towards the defroster. Unfortunately, despite the low sensitivity downward, this first prototype remains relatively sensitive to noise caused by the laminar airflow from the defroster that travels up the windshield of the vehicle due in part to the fact that the rear ports of the microphone assembly open towards this airflow. A plot of the sensitivity of the first prototype to such noise over a frequency band of 20 Hz to 1000 Hz is shown as plot A in FIG. 64.

To reduce the sensitivity of the microphone assembly to the defroster airflow, a windscreen having a very high acoustic resistivity was used in the second prototype. As shown in plot B of FIG. 64, the use of the very high acoustic resistivity windscreen significantly reduced the sensitivity of the microphone to the defroster airflow noise. However, very high acoustic resistivity windscreen adversely made the microphone sensitivity much less directional as shown in the polar plot of FIG. 65.

A third prototype was then constructed and tested whereby acoustic dam 4130 was added to the prototype having the very high acoustic resistivity windscreen. Surprisingly, as shown in the polar plot of FIG. 66, the directional sensitivity of the microphone assembly was recovered despite the use of the very high acoustic resistivity windscreen. Therefore, the benefit of noise rejection provided by the windscreen may be exploited without any loss in directionality.

There are several useful variations on the basic dam. These include forming more than two zones supporting more than one transducer in a single outer housing. Since these zones are acoustically as separate as the outer ports, a single housing can hold multiple transducers to gain the advantage of a large nitration volume and yet have each transducer act as if it were in its own separate housing as far as acoustic directional properties are concerned. It will be appreciated that acoustic dam 4130 could be integral extension of circuit board or microphone housing rather than a separate element. The acoustic dam design frees the designer from the trade-offs of the prior art. Large housings can be used yet act as several smaller ones. Transducers can be aimed internally different from the aiming direction of the external microphone without using ducts that impair higher frequency performance.

One aspect derived from this design is the ability to create highly directional microphones with directional attributes that do not vary with frequency to the degree prior art microphones do. In a typical microphone design, in order to increase the directional aspect from omni-directional through all possibilities to bi-directional, the transducer's internal damping must be lowered. The assignees prior “D” extender designs modestly improved this relationship by adding additional directional pressures. The new acoustic dam allows very directional microphones with very high damping factors. In other words, the acoustic resistance is so high that it swamps out the other variables that cause directional parameters to change with frequency.

To demonstrate the ability of the inventive structure to maintain directional parameters over frequency bands of interest, the third prototype rearview mirror described above (i.e., having the very high acoustic resistance windscreen and the acoustic dam) was placed in a test chamber with the mirror glass face up and in a horizontal plane. The mirror assembly as rotated about a vertical axis extending perpendicularly through the middle of the mirror glass and polar plots were obtained at various frequencies for the driver-side microphone assembly. These polar plots are shown in FIGS. 67-69 in which the 0 degree axis corresponds to the top of the mirror assembly and the 180 degree axis corresponds to the bottom of the mirror assembly. FIG. 67 shows a polar plot at 250 Hz, whereas FIG. 68 shows various plots between 300 Hz and 2 kHz and FIG. 69 shows various plots taken between 3 kHz and 6 kHz. In viewing these plots it will be noted that the plots do not vary significantly from frequency to frequency and that the greatest sensitivity is at about 30 degrees. This ideal insofar as the mirror assembly is typically rotated and tilted relative to the driver so as to have maximum sensitivity to receive sound waves from the driver that reflect off of the windshield and/or headliner of the vehicle.

To test the directionality in a different plane, the same mirror assembly was placed in the test chamber on end such that the axis about which the mirror assembly is rotated being parallel to the axis of the mirror extended along its longest dimension. In these resulting polar plots, the zero degree axis corresponds to an axis that is perpendicular to, and extends in front of, the mirror glass. FIG. 70 shows various polar plots between 300 Hz and 1 kHz, whereas FIG. 71 shows various plots between 3 kHz and 6 kHz and FIG. 18 shows various plots taken between 6.5 kHz and 8 kHz. In these plots, it will again be noted that there is little various in directional sensitivity as a function of frequency. Also, the maximum sensitivity for frequencies between 3 kHz and 8 kHz occurs at about 120 degrees, which would be ideally corresponding to an upwards direction when the mirror assembly is tilted downward by the driver in a normal viewing position.

Finally, by allowing port areas to set aiming direction and effective “D”, the dam design supports the use of any housing styling (even non-symmetrical designs) since port area can be symmetrical and the acoustic dam can form regions of the correct volume. In this case, the advantage takes the form of freedom of physical design, and thus housings that are larger and have more complex exterior shapes can be used.

As suggested above, the above described acoustic dam (or at least a modified version thereof) may be implemented in a microphone assembly having a microphone housing in which two or more transducers are mounted. An example of such a microphone assembly 4220 is shown in FIGS. 73 and 74. This particular embodiment of the inventive microphone assembly is intended for mounting to the top surface of the mirror housing in a manner similar to that disclosed in commonly-assigned U.S. Pat. No. 6,882,734. It will be appreciated, however, that the depicted microphone assembly 4220 could be mounted elsewhere.

Microphone housing 4215 preferably includes front ports 4216 and rear ports 4218, and may include top ports 4217. In the example shown in FIGS. 73 and 74, the two centermost rear ports 4218 are closed as are two of top ports 4217 (the closed ports are shown in dashed lines). As shown in FIG. 73, three zones 4240 a, 4240 b, and 4240 c are formed within microphone housing 4215 by an acoustic dam 4230. First zone 4240 a is common to the fronts of the transducers 4225 a and 4225 b. Second zone 4240 b is formed to the rear of transducer 4225 a and third zone 4240 c is formed to the rear of transducer 4225 b. These zones steer the aiming direction of the first transducer 4225 a to better aim at the driver yet keep the transducers physically facing in opposite directions to gain the advantages in air flow and vibration cancellation. Thus, more than one transducer may be provided in a housing and more than two zones may be formed to thereby provide the freedom to aim the sensitivity of the microphone assembly based on the outer port locations rather than physical orientation of the transducers.

The acoustic dam 4230 forces a definition of the ports 4216, 4217, and 4218 that will contribute to the front and those that will add up to be the rear signal. There will be a center of area that will act as the virtual location for the front and another for the rear. A line through these two centers will form the aiming axis independent of the transducer orientation. In this third depicted embodiment, the rear zones are formed such that the driver-facing microphone transducer 4225 a will aim more into the cab and the rear of the passenger-facing transducer 4225 b aims more away from the cab. This is accomplished by changing to which side of the acoustic dam 4230 the rear ports 4218 connect. In this third embodiment, acoustic dam 4230 extends from the top of the circuit board to the top inner surface of the microphone housing 4215 and extends tightly around all of the upper peripheral edge of transducer 4225 a and tightly around half of the upper peripheral edge of transducer 4225 b. This provides for a tight acoustic seal through the acoustic chamber defined by housing 4215 with the exception of the openings at one side of transducer 4225 b and at the ends of dam 4230.

The inventive microphone construction is preferably located on the back of a rearview mirror assembly housing. Nevertheless, the certain aspects of the inventive microphone may be implemented in microphones mounted at other locations on a mirror assembly, including on the mirror assembly mounting structure, the top, bottom, or sides of the mirror housing, as well as in any other vehicle accessory such as a headliner, sun visor, overhead console, A-pillar, or a console extending between the headliner and a mirror assembly. For example, the above-described acoustic dam may be employed in various microphone assemblies whether used in vehicle applications or any other non-vehicle applications. Additionally, the mounting of two microphone assemblies in a vehicle such that the microphones are spaced apart with an acoustic barrier therebetween like the portion of the rear surface of the mirror housing. For example, if an overhead console is provided, the microphone assemblies could be recessed into the console and spaced apart in a manner similar to the disclosed mirror assembly implementation. Further, if the overhead console protrudes downward from the headliner, the microphone assemblies could be mounted on either side of the console with or without recesses.

The above description is considered that of the preferred embodiments only. Modifications of the invention will occur to those skilled in the art and to those who male or use the invention. Therefore, it is understood that the embodiments shown in the drawings and described above are merely for illustrative purposes and not intended to limit the scope of the invention, which is defined by the following claims as interpreted according to the principles of patent law, including the doctrine of equivalents. 

1. A vehicle accessory comprising: an accessory housing for attaching to a vehicle; at least one transducer carried by the accessory housing; and a microphone interface circuit electrically coupled between the transducers and a remote processing circuit located remote from the vehicle accessory where the microphone interface circuit includes an inverted comb filter for eliminating predetermined frequencies between harmonics of the human voice in a predetermined frequency range.
 2. The vehicle accessory of claim 1, wherein the accessory housing is a mirror housing.
 3. The vehicle accessory of claim 2, the microphone interface circuit further comprising: a noise level detector for adjusting the amplitude of the signal output by the inverted comb filter.
 4. The vehicle accessory of claim 3, wherein the noise level detector samples audio from an analog-to-digital converter that receives audio from the at least one transducer.
 5. The vehicle accessory of claim 1, wherein the inverted comb filter utilizes a fast Fourier transform for determining a fundamental audio frequency of audio received at the at least one transducer.
 6. The vehicle accessory of claim 5, wherein the fundamental audio frequency is used to generate a plurality of adaptive filter coefficients for determining the predetermined frequencies that are to be eliminated.
 7. The vehicle accessory as in claim 1, wherein audio from the inverted comb filter is converted to analog for use by the remote processing circuit.
 8. A vehicle accessory comprising: an accessory housing for attaching to a vehicle; a first transducer carried by the accessory housing and generating a first audio signal; a second transducer carried by the accessory housing and generating a second audio signal; and a microphone interface circuit electrically coupled between the transducers and a remote processing circuit located remote from the vehicle accessory, the microphone interface circuit including an inverted comb filter for eliminating noise located between harmonics of the human voice in a predetermined frequency range.
 9. The vehicle accessory of claim 8, wherein the accessory housing is a mirror housing.
 10. The vehicle accessory of claim 9, the microphone interface circuit further comprising: a noise level detector for adjusting the amplitude of the signal output by the inverted comb filter.
 11. The vehicle accessory of claim 10, wherein the noise level detector samples audio from an analog-to-digital converter that receives audio from the first transducer and second transducer.
 12. The vehicle accessory of claim 8, wherein the inverted comb filter utilizes a fast Fourier transform for determining a fundamental audio frequency of a user's voice.
 13. The vehicle accessory of claim 12, wherein the fundamental audio frequency is used to generate a plurality of adaptive filter coefficients for determining the predetermined frequencies that are to be eliminated by the inverted comb filter.
 14. A vehicle accessory comprising: an accessory housing for attaching to a vehicle; a first transducer carried by the accessory housing and generating a first audio signal; a second transducer carried by the accessory housing and generating a second audio signal; a high frequency boost circuit coupled to the first transducer and second transducer for receiving the first audio signal and second audio signal and for boosting the frequency response at high frequencies to compensate for the effect of noise in the vehicle; and a microphone interface circuit electrically coupled between the first transducer and second transducer and a remote processing circuit located remote from the vehicle accessory where the microphone interface circuit includes an inverted comb filter for eliminating noise located between harmonics of the human voice in a predetermined frequency range.
 15. The vehicle accessory of claim 14, wherein the accessory housing is a vehicular mirror housing.
 16. The vehicle accessory of claim 14, the microphone interface circuit further comprising: a noise level detector for adjusting the amplitude of a signal output by the inverted comb filter.
 17. The vehicle accessory of claim 16, wherein the noise level detector samples audio from an analog-to-digital converter that receives audio from the first transducer and second transducer.
 18. The vehicle accessory of claim 14, wherein the inverted comb filter utilizes a fast Fourier transform for determining a fundamental audio frequency of the user's voice in the frequency domain.
 19. The vehicle accessory of claim 18, wherein the fundamental audio frequency is used to generate a plurality of adaptive filter coefficients for determining the predetermined frequencies that are to be eliminated by the inverted comb filter.
 20. The vehicle accessory of claim 14, wherein the high frequency boost circuit boosts the frequency response such that a frequency response curve associated with the first transducer and second transducer is not flat and independent of the effect of the vehicle.
 21. The vehicle accessory of claim 14, wherein the high frequency boost circuit boosts the frequency response between about 3.5 and 5 KHz.
 22. A vehicle accessory comprising: an accessory housing for attaching to a vehicle; a plurality of transducers carried by the accessory housing and generating a plurality of respective audio signals; a microphone interface circuit electrically coupled between the plurality of transducers and a remote processing circuit located remote from the vehicle accessory, the microphone interface circuit including at least one inverted comb filter for eliminating predetermined frequencies between harmonics of the human voice in a predetermined frequency range; and a noise level detector for adjusting the amplitude of a signal output of the inverted comb filter.
 23. The vehicle accessory of claim 22, wherein the accessory housing is a rearview mirror assembly housing.
 24. The vehicle accessory of claim 22, wherein the at least one inverted comb filter utilizes a fast Fourier transform for determining a fundamental audio frequency of a user's voice in the frequency domain.
 25. The vehicle accessory of claim 24, wherein the fundamental audio frequency is used to generate a plurality of adaptive filter coefficients for determining the predetermined frequencies that are to be eliminated by the inverted comb filter.
 26. The vehicle accessory of claim 22, wherein the microphone interface circuit further comprises: an digital-to-analog converter for converting audio adjusted in amplitude from the at least one inverted comb filter into an analog signal for use by the remote processing circuit. 